Phase aligned interleaved sampling of multiple data channels

ABSTRACT

Provided is a method for processing data samples from a plurality of data channels. The method may include obtaining a plurality of data samples from the plurality of data channels. Obtaining the plurality of data samples may involve successively obtaining a data sample from each data channel of the plurality of data channels. Successively obtaining a data sample from each data channel may be performed a plurality of times during a specified time period. Each data sample of the plurality of data samples may be associated with a respective sample time, and each respective sample time may be relative to a single specified reference point in time. The method may further include, for each data sample of the plurality of data samples, determining a time-dependent coefficient value that may correspond to the sample time associated with the data sample, and applying the determined time-dependent coefficient value to the data sample.

PRIORITY DATA

This application is a divisional application of U.S. application Ser.No. 12/847,656 titled “Phase Aligned Sampling of Multiple Data ChannelsUsing a Successive Approximation Register Converter” filed Jul. 30,2010, whose inventors are Garritt W. Foote and Hector Rubio, and whichis hereby incorporated by reference in its entirety as though fully andcompletely set forth herein.

FIELD OF THE INVENTION

This invention relates to a system and method of measuring and filteringone or more data channels using a successive approximation registerconverter.

DESCRIPTION OF THE RELATED ART

Delta-sigma modulators may be used in industrial and sensor measurementproducts to obtain high resolution analog-to-digital conversions and toeliminate cost, power, and usability issues associated with programmablegain amplifiers. And, since delta-sigma modulators integrate over aperiod of time, they may be a good choice to provide notch filtering ofdata to remove noise from power line harmonics. In some products (e.g.,products intended for low-bandwidth applications) multiple data channelsmay be multiplexed into a single delta sigma ADC. In other products(e.g., higher cost products) each data channel (e.g., channel) may havea dedicated delta-sigma analog-to-digital converter (ADC) and amplifierchain for simultaneous, phase-matched measurements between channels.

However, for a variety of reasons (e.g., operational characteristics) itmay be difficult to trade off power consumption, bandwidth andresolution in designs that use delta-sigma modulators. Also, the use ofdelta-sigma modulators may restrict advances in reducing response time,reducing power consumption and reducing inter-channel phase delay forpower-line filtering applications. Lastly, in a single delta-sigma ADCsystem, it may be difficult to make effectively simultaneousmeasurements. Thus while delta-sigma converters may provide certainadvantages to system designers they may also present certain problems.

Accordingly it may be desirable to provide a system and method formeasuring and filtering one or more channels using a successiveapproximation register (SAR) converter.

SUMMARY OF THE INVENTION

Provided is a method for processing a plurality of data sets, where eachdata set of the plurality of data sets may comprise a plurality of datasamples. In some embodiments, the method may include receiving, in asequence, each data sample of the plurality of data sets. Additionally,adjacent data samples in the sequence may correspond to differentcoefficient values.

Receiving each data sample of the plurality of data sets may includereceiving each data set through a different corresponding data channelof a plurality of data channels. The method may also include performing,for each received data sample, one or more of the following steps:determining a corresponding position within the sequence, identifyingthe corresponding data channel for each received data sample, obtaininga coefficient value corresponding to the determined correspondingposition, and calculating, according to the obtained correspondingcoefficient value, a weighted value corresponding to the data sample.

In certain embodiments, determining a corresponding position within thesequence, obtaining a coefficient value corresponding to the determinedcorresponding position and calculating a weighted value corresponding tothe data sample may all be performed for a current data sample prior toreceiving a next data sample of the plurality of data samples. Also, insome embodiments, each coefficient value may be different from a mostrecent previously determined coefficient value. According to someembodiments, adjacent data samples in the sequence correspond todifferent data channels of the plurality of data channels.

In certain embodiments, calculating a weighted value corresponding tothe data sample may involve multiplying the received data sample by theobtained corresponding coefficient value to produce a weighted valuecorresponding to the data sample. And, obtaining a coefficient value mayinclude obtaining a coefficient value corresponding to the identifiedcorresponding data channel

Also provided is a method for processing data samples from a pluralityof data channels. The method may include obtaining a plurality of datasamples from the plurality of data channels. Obtaining a plurality ofdata samples may involve successively obtaining a data sample from eachdata channel of the plurality of data channels and may involve receivingdata samples of the plurality of data samples at a specified rate.Successively obtaining a data sample from each data channel may beperformed a plurality of times during a specified time period. Also,successively obtaining a data sample from each data channel may includesuccessively obtaining a data sample from each data channel in aspecified order corresponding to a specified ordering of the pluralityof data channels.

Each data sample of the plurality of data samples may be associated witha respective sample time, and each respective sample time may berelative to a single specified reference point in time. In someembodiments, the single specified reference point in time may be locatedwithin the specified time window and may correspond to the start of thespecified time window. The method may further include, for each datasample of the plurality of data samples, determining a time-dependentcoefficient value that may correspond to the sample time associated withthe data sample, and applying the determined time-dependent coefficientvalue to the data sample. Also applying may involve multiplying the datasample by the respective time-varying coefficient value to produce aweighted data sample.

In certain embodiment, the method may also include generating, for eachdata channel of one or more data channels of the plurality of datachannels, an effective data sample from two or more weighted datasamples corresponding to the data channel. And generating may involvearithmetically combining the two or more weighted data samples.

Also provided is an apparatus for processing a sequence of data samples.In some embodiments the apparatus may include an input that may beconfigured to receive a sequence of data samples. And, the sequence ofdata samples may include at least one respective data sample from eachdata channel of an ordered set of two or more data channels. Also, theapparatus may include first circuitry that may be configured to identifya respective position, within the sequence of data samples, of eachreceived data sample of the received sequence of data samples.Accordingly, the first circuitry may include a sample index registerand, in order to identify a respective position of each received datasample of the received sequence of data samples, the first circuitry maybe configured to set the sample index register to a specified value andthen, for each received data sample, set the sample index register to acurrent value indicative of the number of data samples received sincethe index register was last set to the specified value. The specifiedvalue may be indicative of the respective position, within the sequenceof data samples, of a leading data sample of the sequence of datasamples.

In some embodiments, the apparatus may include coefficient circuitrythat may be configured to produce a respective coefficient value foreach received data sample according to the identified respectiveposition of the received data sample. Producing the respectivecoefficient value for each received data sample may involve using thecurrent value of the sample index register. And, for each of at leasttwo successively received data samples of the received sequence of datasamples, where each successively received data sample may correspond toa different respective data channel, the coefficient circuitry may beconfigured to produce a different respective coefficient value for eachof at least two successively received data samples.

In certain embodiments, the apparatus may include computation circuitrythat may be configured to calculate a respective weighted value for eachreceived data sample according to the obtained respective coefficientvalue of the received data sample. And, to calculate a respectiveweighted value for each received data sample, the computation circuitrymay be configured to multiply a data value corresponding to the receiveddata sample with the produced respective coefficient value of thereceived data sample.

BRIEF DESCRIPTION OF THE DRAWINGS

A better understanding of embodiments of the present invention can beobtained when the following detailed description of the preferredembodiment is considered in conjunction with the following drawings, inwhich:

FIG. 1 is a diagram illustrating an analog-to-digital converter (ADC)system according to an embodiment;

FIG. 2 is a block diagram of a notch rejection filter according to anembodiment;

FIGS. 3A and 3B are charts, respectively showing a time domainrepresentation and a frequency response curve of a 20 mS unitrectangular filter window;

FIGS. 4A and 4B are charts, respectively showing a time domainrepresentation and frequency response curve of a 16.6 mS unitrectangular filter window;

FIGS. 5A and 5B are charts, respectively showing a time domainrepresentation and a frequency response curve for a second orderconvolution of a 16.6 mS unit rectangular filter window and a 20 mS unitrectangular filter window;

FIGS. 6A and 6B are charts, respectively showing a time domainrepresentation and a frequency response curve for a fourth orderconvolution of two 20 mS unit rectangular filter windows and two 16.6 mSunit rectangular filter windows;

FIG. 7A is a chart showing a time domain representation of a basefunction corresponding to the convolution of four functions;

FIG. 7B is a chart showing a time domain representation of functioncorresponding to a fourth order integration of the base function shownin FIG. 7A;

FIGS. 8A and 8C are charts respectfully illustrating filtering curvesand noise levels in an SAR based system and a delta-sigma based system;

FIGS. 8B and 8D are charts, respectfully illustrating noise shaping inan SAR based system and a delta-sigma based system;

FIG. 9A is a chart illustrating noise density versus frequency for anSAR based system;

FIG. 9B is a chart illustrating the relationship between sampleresolution and oversampling ratio for a SAR based system;

FIG. 9C is a chart illustrating noise density versus frequency for adelta-sigma based system;

FIG. 9D is a chart illustrating the relationship between sampleresolution and oversampling ratio for a delta-sigma based system;

FIGS. 10A and 10B are charts, respectfully illustrating, for a SAR basedsystem, the relationship between sample resolution and power and therelationship between sample resolution and output rate;

FIGS. 10C and 10D are charts, respectfully illustrating, for adelta-sigma based system, the relationship between sample resolution andpower and the relationship between sample resolution and output rate;

FIG. 11A is a diagram illustrating the sampling of data over fourconsecutive integration periods in a delta-sigma based system;

FIG. 11B is a diagram illustrating the sampling of data over fourinterleaved integration periods in a SAR based system according tovarious embodiments;

FIG. 12A is a diagram illustrating interleaved sampling with one sampletaken per sample period;

FIG. 12B is a diagram illustrating interleaved sampling with multiplesamples taken per sample period according to an embodiment;

FIG. 13A is a diagram illustrating average measurement times for fourgroups of samples acquired during four consecutive sampling periods;

FIG. 13B is a diagram illustrating average measurement times for fourgroups of samples acquired during four interleaved sampling periodsaccording to an embodiment;

FIG. 14A is a diagram illustrating the application of a weightingfunction to samples from four channels, where the same weightingfunction value may be applied to multiple associated samples;

FIG. 14B is a diagram illustrating the application of a weightingfunction to samples from four channels, where different weightingfunction values may be applied to multiple associated samples;

FIGS. 15A, 15B and 15C respectfully depict multiply accumulatorcircuitry according to a first embodiment, a sequence of data samples,accumulator contents during the processing of the sequence of datasamples;

FIGS. 15D and 15E respectfully depict multiply accumulator circuitryaccording to a second embodiment and accumulator contents during theprocessing of the sequence of data samples;

FIG. 16A-16H are charts illustrating various relationships between aweighting function, rectangle functions that may be convolved to formthe weighting function and derivatives of weighting and rectanglefunctions;

FIGS. 17A and 17B are charts, respectfully illustrating a weightingfunction and a second order derivative of the weighting function;

FIGS. 17C-17E respectfully show a first number sequence correspondingthe second order derivative of the weighting function, a second numbersequence corresponding a first order derivative of the weightingfunction and a third number sequence corresponding to the weightingfunction; and

FIG. 18 is a flow chart illustrating a method for processing a pluralityof data sets.

While the invention is susceptible to various modifications andalternative forms, specific embodiments thereof are shown by way ofexample in the drawings and are herein described in detail. It should beunderstood, however, that the drawings and detailed description theretoare not intended to limit the invention to the particular formdisclosed, but on the contrary, the intention is to cover allmodifications, equivalents and alternatives falling within the spiritand scope of the present invention as defined by the appended claims.

DETAILED DESCRIPTION OF THE EMBODIMENTS

In the following description, numerous specific details are set forth toprovide a thorough understanding of the present invention. However, onehaving ordinary skill in the art should recognize that the invention maybe practiced without these specific details. In some instances,well-known circuits, structures, and techniques have not been shown indetail to avoid obscuring the present invention.

Overview

In some embodiments, a successive approximation register (SAR) convertermay be used in applications and systems that otherwise use delta-sigmaconverters to provide similar or improved performance (e.g., similarlyhigh resolution) and to provide additional advantages. To this end, aSAR converter may be oversampled at a rate higher than an intendedoutput data rate. Also, a SAR converter may be combined with logic tooversample and to average (or integrate) data samples before returning aresulting value as a useful output data value. A SAR converter, perhapsin association with combined logic, may provide a flexible convertercircuit that may allow power, data rate, and resolution to be traded offfor each other. Additional advantages of a SAR based solution mayinclude faster response, lower power, and less inter-channel phase delayfor power-line filtered applications. The SAR based solution may alsoenable effectively simultaneous multi-channel measurements with a singleanalog-to-digital converter (ADC) and multiplexed inputs. SAR convertersmay provide various advantages over delta-sigma modulators since, forexample, the noise shaping of a delta-sigma modulator may limit theuseful range of tradeoffs that may be made and so a delta-sigma baseddesign may have less flexibility than a SAR based design

Some embodiments may include one or more digital integrators to generatefilter coefficients for various filter responses which may trade offpower-line notch filter performance for integration time. In someembodiments, a single logic implementation of integrators may be used togenerate various filter functions that may be convolutions of simplerectangular windows. Also, digital integrators may generate variousfilter functions that may be products of sin(x)/x responses. In certainembodiments, filter coefficients may be generated according toeliminating the need for memory or look-up tables.

In certain embodiments, an ADC serial interface may be coupled to ashift-and-add multiplier so the multiplication of filter coefficientswith ADC values may be accomplished without the use of a more costlyhardware multiplier. The multiplication may be performed by shifting thecoefficient value with each ADC serial clock and either adding it intoan accumulator or not based on the next bit value of the ADC data.

According to some embodiments, multiple channels may be scanned (e.g.,interleaved) over a single integration period and samples may beaveraged as each sample is taken. Within a single integration periodmeasurements may be obtained for all channels with power-line notchfilter rejection that is dictated by the length of the period. This maybe contrasted with delta-sigma based designs in which only one channelmay be sampled per integration period. This approach may enable data tobe obtained at similar (e.g., equal) rate to a comparable designfeaturing a delta-sigma and amplifier chain per channel, but atsubstantially lower cost and power.

Some embodiments may support an ADC operating with “burst mode” timing.In this mode, extra time may be provided for a relatively low poweramplifier to settle and then multiple samples of data may be obtained ata high rate before switching to a new channel and repeating the process.This timing method may enable the use of low power amplifier with arelatively fast ADC. This approach may enable the design andconstruction of more cost effective solutions and may also allow lowercost products (e.g., slow settling amplifiers) to be used in systemsthat previously required higher cost versions (e.g., fast settlingamplifiers).

In certain embodiments, a weighting function may be applied to multiplechannels that may not be identical for each channel (e.g., weightingcoefficients applied to one channel may differ from weighting samplesapplied to a different channel). Instead, the weighting function mayincrement according to a single master weighting function with eachchannel change. By supplying each channel with a different, asymmetricalweighting function the multiple channels may be effectively phasealigned. This may allow a single amplifier and ADC with multiplexedinput channels to have the phase aligned characteristics of a moreexpensive system (e.g., a system with an amplifier and converter perchannel).

FIG. 1

FIG. 1 depicts an analog to digital converter system 100 according tovarious embodiments. System 100 may include SAR ADC 114, analogfront-end 116, SAR interface unit 104, microcontroller unit 102 and bus106. Analog front-end 116 may be connected to plurality of analogchannels (e.g., channels “Ch1 . . . ChN”). Analog front-end 116 may actas a multiplexer and may provide an analog signal (e.g., an analogsignal from a selected one of channels “Ch1 . . . ChN”, an amplifiedanalog signal, an output analog signal) to SAR ADC 114. SAR ADC 114 maysample the analog signal (e.g., regularly, in response to receiving aconvert signal), convert the analog signal to a digital sample (e.g.digital representation, a digital value) and output the digital sample(e.g., output serially, output as part of a series or sequence of datasamples, output as part of a data stream) to SAR interface unit 104. SARinterface unit 104 may filter and/or average data samples received andprovide corresponding measurements to microcontroller unit (MCU) 102.

SAR interface unit 104 may include, for example, bus interface 108, scancontrol 110 and notch rejection filter (NRF) 112. MCU 102 may instruct(e.g., via signal start acquisition 150) the scan control 110 tocommence data acquisition. MCU 102 may also configure the acquisitionby, for example, writing (e.g., via bus 106 and bus interface 108) toscan control 110. MCU 102 may configure the acquisition by writing tocontrol structures of scan control 110 and/or issuing commands to scancontrol 110. Configuring the acquisition may involve, for example, MCU102 specifying one or more of the following: channels to be sampled,sampling rates, oversampling rates, filter functions, filter orders,multiplexing schemes.

Scan control 110 may drive (e.g., generate, output, control) signals(e.g., control signals, clocks) that may coordinate and control othersystem components (e.g., SAR ADC 114, analog front end 116 and NRF 112)so that acquisition and filtering may be properly carried out. Forexample, scan control 110 may drive front end control 156 (e.g., frontend control signals, front end control bus) so that the appropriatechannel (e.g., one of Ch1 to ChN) is selected at the appropriate time.For example, front end control 156 may carry information that may beused to control a channel select multiplexer within analog front end116.

Scan control 110 may also generate a convert signal output (e.g., onconvert 154) to instruct SAR ADC 114 to perform a conversion (e.g., takea sample, sample an analog signal). Scan control 110 may also provide aserial clock (e.g., a clock for serial communications, a clock driven onserial clk 158) to SAR ADC 114 and receive ADC serial data (e.g., onserial data 160) that may be clocked by the provided serial clock.

Also, scan control 110 may receive inputs (e.g., configuration inputs)from NRF 112 and may send signals (e.g., control signals, data) to NRF112. For example, NRF 112 may provide a window length input to scancontrol 110 (e.g., to inform scan control 110 of the length of a filterwindow to be used). Scan control 110 may output a convert pulse signal(e.g., a pulsed signal that may correspond to convert signal 154) to NRF112 (e.g., to notify NRF 112 that new sample data may arrive). Scancontrol 110 may also generate and output a latch control signal (e.g.,latch_SDI) which may be used by NRF 112 to capture ADC serial data(e.g., data samples from the ADC, data samples transmitted on serialdata 160).

NRF 112 may process received ADC serial data (e.g., according toconfiguration settings, according to a selected filter) and may supplyprocessed (e.g., filtered, weighted) data to bus interface 108 (e.g., inresponse to a read by MCU 102). Data may be supplied to bus interface108, via data out signals. MCU 102, or some other device that may beconnected to SAR interface unit 104, may obtain (e.g., by reading, byrequesting) ADC data (e.g., ADC filtered data) from SAR interface unit104 (e.g., from NRF 112). In some embodiments, MCU 102, or anotherconnected device, may obtain ADC data through bus transactions (e.g.,bus reads, direct memory access reads) on bus 106, and thesetransactions on bus 106 may be converted (e.g., translated) into bustransactions between bus interface 108 and NRF 112 (e.g., on depictedsignal lines address/data, rd/wr, data out; on internal bus lines). Whenan acquisition is complete, scan control 110 may signal completion toMCU 102 by asserting signal acquisition done 152.

FIG. 2

FIG. 2 illustrates NRF 112 according to some embodiments. Depicted NRF112 may represent an embodiment that may process a data stream that maybe formed by interleaving data samples from different channels. Forclarity, circuitry that may allow NRF 112 to support other operationalmodes (e.g., a mode that processes a data stream from a single channel)is not shown. In certain embodiments, mode switching logic may affectrelations between channel index register 216 and the sample indexregister 224. The implementation depicted in FIG. 2 assumes SAR ADC 114returns the most significant bit (MSB) of data first (e.g., to NRF 112)but in other embodiments the least significant bit (LSB) of data may bereturned first. In the depicted embodiment the maximum order of theimplemented filters may be represented by “P” and the number of channelsmay be represented by “N”. The values of “P” or “N” are positiveintegers and may vary depending on the embodiment. For example, inembodiments where the filter order is the same as the number ofchannels, “P” will equal “N”. Overall, the respective values of “P” and“N” may be specified or selected according to the requirements andspecifications of each system and/or application.

As depicted in FIG. 2, some embodiments of NRF 112 may comprise severalsub-blocks. For example, NRF 122 may comprise a coefficient generator(CG) 210 and a multiply accumulator (MAC) 250. NRF 112 may also comprisevarious inputs which may include for example, Filter Select 286. Thisinput may be used, for example, to select a filter window to be applied.Another input may be Filter Order Select 288, which may be used tospecify the order of the selected filter window selected. In certainembodiments, the order of the selected filter may be obtained from alook-up table (LUT), where the LUT may be stored in memory (e.g., arandom access memory—RAM, a read-only memory—ROM, a non-volatileRAM—NVRAM, a Flash ROM, as combination logic) and where a LUT entrycorresponding to a selected filter may provide the order of the selectedfilter. The input Convert Pulse 280 may be provided on certainembodiments, and Convert Pulse 280 may, for example, carry a pulsedversion of the convert signal 154 that is sent to the ADC 114. A convertsignal received at input Convert Pulse 280 may mark the start of a newdata sample/acquisition. ADC data may be provided (e.g., serially) toNRF 112 on input ADC Serial Data 284 and, as previously mentioned,serial data may be provided MSB bit first. Another input may be ADCLatch Serial Data 282. The input ADC Latch Serial Data 282 may tell NRF112 when to latch the data provided at input ADC Serial Data 284. Incertain embodiments, the serial clock signal 158 sent to the ADC 114 maybe applied to input ADC Latch Serial Data 282. In some embodiments, thetime between a convert pulse being received on input Convert Pulse 280and a corresponding first data bit being received on ADC Serial Data 284may be large enough to enable a filter constant to be generated and bemade available. For example, for a maximum filter order of P, the firstdata bit may be supplied at least P+1 clocks after a correspondingconvert pulse is received.

Coefficient Generator

CG 210 may, in some embodiments, include some or all of the followingcomponents. As depicted in FIG. 2, coefficient generator 210 may includea channel index counter that may increment on every convert pulse (e.g.,every convert pulse received on input Convert Pulse 280) and may reset(e.g., to zero) on specified occasions (e.g., when the count valuereaches the number of channels minus one). Thus, the channel indexcounter may effectively count through each channel. As in the depictedembodiment, the channel index counter may include adder 214 coupled tochannel index register 216. Adder 214 may be used to increment the valueof channel index register 216 in response to a convert pulse beingreceived on input Convert Pulse 280. In certain embodiments where thenumber of channels may be a power of two, channel index register 216 maybe reset through a normal counter overflow and no extra reset logic maybe involved. CG 210 may also include channel index comparator 218 whichmay compare the value of channel index register 216 against a specifiedvalue (e.g., maximum channel count value, “N−1”) and, when there is amatch, generate an update signal (e.g., an update enable signal) for usein coefficient generator 210.

As depicted in FIG. 2, CG 210 may include a sample index counter thatmay count every “N” channels (e.g., every sample aggregate) and so thesample index counter may be able indicate (e.g., track, output, supply)the current tap in the filter window. The sample index counter mayinclude sample index register 224 coupled to adder 222 and channel indexcomparator 218. In some implementations, sample index register 224 maybe updated upon receiving an update signal (e.g., from channel indexcomparator 218).

According to some embodiments, CG 210 may also include base functiongenerator 226. Base function generator 226 may be coupled to the outputof sample index register 224 and to input Filter Select 286. In certainembodiments, base function generator 226 may include a LUT and eachoutput value of base function generator 226 may correspond to a selectedentry in the LUT. LUT entries may be selected based on the output ofsample index register 224 and the value of input Filter Select 286. Incertain embodiments, the LUT of base function generator 226 may beimplemented as combinational logic coupled to the output of sample indexregister 224 and input Filter Select 286 or the LUT may be implementedas a table in non-volatile memory (e.g., read-only memory, Flashmemory).

In some embodiments the base function generator may generate a series(e.g., a sequence) of data values corresponding to a base function andthe base function may be a specified order derivative of a filterfunction (e.g., a weighting function, a coefficient function). Thespecified order derivative function may comprise scaled unit deltafunctions separated by zero values. The series of data values output bythe base function generator may correspond to the values of the scaleddelta functions (e.g., 4, 7, 1, 3) separated by significant numbers ofconsecutive zero values (e.g., by ten consecutive zeros, by 43consecutive zeros, by 235 consecutive zeros). According to someembodiments, base function generator 226 may comprise a counter. Thecounter may count (e.g., in parallel to the sample index counter) thenumber of zeros between deltas stored in a smaller LUT or ROM and outputthe stored value of the delta when it reaches its terminal count.

In certain embodiments, coefficient generator 210 may include one ormore accumulators. In the depicted embodiment, coefficient generator 210may include “P” accumulators. Each accumulator of the “P” accumulatorsmay comprise an accumulator register and coupled adder circuitry. Forexample, in FIG. 2, accumulator “1” may comprise accumulator registerACC[1] 230 and adjoining adder circuitry 228, accumulator “2” maycomprise accumulator register ACC[2] 234 and adjoining adder circuitry232 and so on up to accumulator “P” which may comprise accumulatorregister ACC[P] 238 and adjoining adder circuitry 236. Note that, forreasons of clarity, accumulators “2” to “P−1” are not depicted in FIG.2. Each accumulator (and corresponding accumulator register) maycomprise a data input, data output, clock input and enable input. Theaccumulators may be coupled to form a series (e.g., chain, sequence) ofaccumulators, where the data output of one accumulator may connect tothe data input of a successive adjoining accumulator (e.g., to the inputof an adder in the successive adjoining accumulator).

This arrangement may allow, for example, the output of each accumulator(e.g., accumulator register) in the series of accumulators (except thelast accumulator in the series) to be added to the contents of the nextrespective accumulator in the series and the updated value stored in thenext respective accumulator in the series. For example, adder 232 ofaccumulator “2” may add the value presented on the data output ofaccumulator “1” (e.g., the contents of accumulator register ACC[1] 230)to the current value of accumulator “2” (e.g., the contents ofaccumulator register ACC[2] 234) and store the updated value intoaccumulator “2” (e.g., into accumulator register ACC[2] 234).

An input to the first accumulator in the chain (e.g. an input to adder228) may be driven by an output of base function generator 226. In someembodiments, the chain of accumulators may be used to integrate theoutput of base function generator 226 (e.g., when the base functioncorresponds to a specified order derivative of a weighting function) inorder to generate a series of filter coefficients. The coefficientgenerator may support (e.g., generate coefficients for) various basefunctions and each supported base function may correspond to a differentorder derivative of a weighting function. For example, a first basefunction may correspond to a fourth order derivative of a firstweighting function and a second base function may correspond to a sixthorder derivate of a second weighting function.

Each successive accumulator in the series of accumulators may correspondto successively higher order integral of the base function. So, forexample accumulator “1” may correspond to a first order integral of thebase function, accumulator “2” may correspond to a second order integralof the base function and accumulator “P” may correspond to a “Pth” orderintegral of the base function. Each accumulator in the series ofaccumulators may output a series of values corresponding to a seriesvalues output by the base function generator. For example, the basefunction generator may output a sequence of values corresponding to a5^(th) order derivative of a first weighting function and the fifthaccumulator in the series (e.g., accumulator “5”) may output sequence ofvalues that corresponds to a 5^(th) order integral of 5^(th) orderderivative of the first weighting function (e.g., that corresponds tothe first weighting function). Consequently, the fifth accumulator mayoutput a sequence of values corresponding to the first weightingfunction itself. Similarly, the base function generator may output asequence of values corresponding to a 3^(rd) order derivative of asecond weighting function and the third accumulator in the series (e.g.,accumulator “3”) may output a sequence of values that corresponds to a3^(rd) order integral of 3^(rd) order derivative of the second weightingfunction (e.g., that corresponds to the second weighting function).

The output of each accumulator (e.g., accumulator registers ACC[1] toACC[P]) may be coupled to an input of multiplexer 240 and a controlinput of multiplexer 240 may be coupled to Filter Order Select 288.Thus, in certain embodiments, the order of the selected filter may beused to select which accumulator (e.g., which accumulator data output)will form the coefficient output of coefficient generator 210 tomultiply accumulator 250. Note that in some embodiments, “P” maycorrespond to the maximum order of filter supported by the embodiment.

Multiply Accumulator

As depicted in FIG. 2, some embodiments of multiply accumulator 250 mayinclude shifter 254, adder 260, multiplexer 262 and “M” resultaccumulators including result accumulators RACC[M−1] 264, RACC[M−2] 266to RACC[0] 268. Note that shifter 254, adder 260 and multiplexer 262represent one or more embodiments capable of performing mathematicaloperations (e.g. multiply-accumulate) on data (e.g., samples). However,other circuitry may be used (e.g. a multiplier unit, an arithmetic unit,a logical unit) and the circuitry used (e.g. adder 260) may be capableof performing a range of functions (e.g., functions such as add,subtract, limit, round, or, AND, NOR, NAND, etc.)

Note that “M” may be equal to or greater than “N” where “N” mayrepresent the number of channels in the system and where “N” may be aninteger greater than or equal to two. For reasons of clarity, resultaccumulators RACC[M−3] to RACC[1] are not depicted. When a new filtercoefficient is generated (e.g., by coefficient generator 210), it may beloaded in shifter 254 at a shifted (e.g., offset) position. The shiftedposition may correspond to the value of ADC resolution minus one and theshift may equate to multiplying the coefficient by a factor of 2^[ADCResolution−1]. This multiplication factor (e.g. 2^[ADC Resolution−1])may correspond to the positional value of the MSB of data items receivedfrom ADC 112. If the MSB of a data item received from ADC 112 is set toone, the shifted coefficient value may be added to the contents of RACC[M−1] 264. If the MSB of a data item received from ADC 112 is set tozero, the shifted coefficient value may not be added to the contents ofRACC[M−1] 264. After a coefficient value is loaded (e.g., at an offsetposition) in shifter 254, whenever a next data item bit is latched(e.g., latched from ADC Serial Data 284), the coefficient value held inshifter 254 may be shifted right (down) one bit in order to update thevalue of the multiplication according to the value of the next bit to beshifted from the ADC. Note that multiplexer 240 may be used to selectwhich accumulator in CG 210 may provide filter coefficient.

As previously mentioned, multiply accumulator 250 may include resultaccumulator RACC[M−1], where M is equal to or greater than N (the numberof channels in the system). This register (e.g., RACC[M−1] 264) may holdthe result of each multiply-accumulate operation in the circuit.

In certain embodiments, the updating of RACC[M−1] 264 (e.g., to storeresults of a multiply-accumulate operation) may be enabled (or not)depending on the value of a data bit that may be in the process of beinglatched from input ADC Serial Data 284. For example, in certainembodiments, RACC[M−1] 264 may be updated if ADC Serial Data 284 isdriven high and the input ADC Latch Serial Data 282 transitions from lowto high (e.g., transitions to latch the data). In one embodiment, the“AND” function may be implemented using circuitry (e.g. AND gate 256).If RACC[M−1] 264 is enabled for update, the current value of RACC[M−1]264 may be added (e.g., by adder 260) to the value of shifter 254 andthe result stored back into RACC[M−1] 264. By this or other means, amultiply and accumulate operation may be implemented without storing thevalue read from ADC 114 (e.g., a data item received on input ADC SerialData 284).

Whenever a new channel is converted, the value of register RACC[M−1] 264may be stored in the next register (e.g. RACC[M−2] 266) and the oldestvalue calculated (e.g., the value corresponding to the next channel insequence, the value stored in RACC[0] 268) may be loaded into RACC[M−1]264 so that it may be used for the next multiply and accumulateoperation (e.g., with the next value read from ADC 114). Multiplexer 262may be used to select the input to RACC[M−1] 264. Formultiply-accumulate updates, multiplexer 262 may select the output ofadder 260 as the input to RACC[M−1] 264. Alternatively, when there is achange of channel (e.g., indicated by input Convert Pulse 280 beingdriven high), multiplexer 262 may select the output of RACC[0] 268 asthe input to RACC[M−1] 264. In one embodiment, “OR” circuitry 258 mayenable RACC[M−1] 264 to be updated from adder 260 or to receive a changeof channel value from RACC[0] 268. In some embodiments, accumulatorregisters RACC[M−1] 264 to RACC[0] 268 may be used to hold the datavalues for all the channels (the channel currently being processed maybe held in RACC[M−1] 264) so only one multiply and accumulate circuitmay be needed for all the channels. In some embodiments, data may berotated (e.g. every time a new channel is selected) through registersRACC[M−1] 264 to RACC[0] 268 in sequence with data items (from differentchannels) arriving from ADC 114. Thus, some embodiments may not utilizea multiplexer to route channel data held in other registers (e.g.,RACC[M−2] 266 to RACC[0] 268) to the multiply-and-add circuit. In someembodiments, by the end of a scan (e.g. when sample index register 244holds a value corresponding to the filter window size, when channelindex register 216 equals “N−1”) the filter results may be ordered bychannel in the result accumulation register RACC[M−1:0] according totheir index.

Filter Window Design

A notch rejection filter window may be a rectangular filter window(e.g., a rectangular filter window of length T) which may have a lowpass frequency response and which may reject frequencies that are aninteger multiples of a target frequency (e.g., F₀=1/T). Notch rejectionat two frequencies (e.g., F_(A) and F_(B)) may be provided by the samefilter by convolving, in the time domain, two rectangle filter windowsof different lengths (e.g., one rectangular filter window may be oflength T_(A)=1/F_(A) and one rectangular filter window may be of lengthT_(B)=1/F_(B)). This convolved filter window may have rejection notchesat frequencies that are multiples of F_(A) and rejection notches atfrequencies that are multiples of F_(B). The length of the filter windowmay be the sum of the two window lengths (e.g., equal to T_(A)+T_(B))and so may be smaller and more energy efficient than a rectangularfilter window of length that is the least common multiple of the twofrequencies (e.g., the frequency that equals both n*T_(A) and m*T_(B),where n and m are positive integers). Furthermore, if it is beneficialto have higher rejection (e.g., wider notches) at a target frequency(e.g., frequency F_(A)), two rectangular windows of the same length(e.g., of length T_(A)=1/F_(A)) may be convolved to get a frequencyresponse with a rejection that may be twice as big (in logarithmicscale) at the target frequency. In this case, the length of the filterwindow may be twice the period of the target frequency (e.g. 2*T_(A)).These two concepts may be used in combination to generate a filterwindow with as many rejection frequencies (e.g., rejection notches) andrejection magnitude per frequency (e.g., rejection notch widths) asneeded. The total “order” of a filter constructed like this maydetermined by the number of rectangular filter windows that wereconvolved with each other to generate the desired filter window.

The following figures (e.g., FIGS. 3A-7B) are charts depicting filterwindows and their corresponding frequency responses for both exemplaryrectangular filter windows and for exemplary filter windowscorresponding to convolutions of multiple rectangular filter windows.These examples use a sample rate of 8192 Hz, a discrete time convolutionover the sampled windows and a normalized frequency response.

FIG. 3A depicts a time domain representation of a rectangular filterwindow 300 of length 20 mS and unit amplitude. FIG. 3B depicts afrequency response curve 350 that may correspond to filter window 300.Note the notch in frequency response curve 350 at a 50 Hz, the notchfrequency corresponding to the reciprocal of the length of therectangular filter window (e.g., 20 mS).

FIG. 4A depicts a time domain representation of a rectangular filterwindow 400 of length 16.67 mS and unit amplitude. FIG. 4B depicts afrequency response curve 450 that may correspond to filter window 400.Note the notch in the frequency response curve 450 at 60 Hz correspondsto the reciprocal of the length of the rectangular filter window length(e.g., 16.67 mS).

FIG. 5A depicts a time domain representation of a filter window 500 oflength 36.67 mS (e.g., 300 integer coefficients generated at 8192samples/s) and maximum amplitude of approximately 136. Filter window 500may be produced by convolving rectangular filter window 300 andrectangular filter window 400. Consequently, the length of filter window500 (e.g., 36.67 mS) may equal the length of filter windows 300 (e.g.,20 mS) added to the length of filter window 400 (e.g., 16.67 mS). FIG.5B depicts a frequency response curve 550 that may correspond to filterwindow 500. Those familiar with the art may appreciate that the twodepicted notches in the frequency response curve 550 (e.g., one notch at50 Hz, one notch at 60 Hz) may, for example, correspond to thereciprocal of the lengths (e.g., 1/16.67 mS, 1/20 mS) of the tworectangular filter windows (e.g., 300 and 400) that may be convolved tocreate filter window 500.

FIG. 6A depicts a time domain representation of a filter window 600 oflength 73.33 mS (e.g., 600 integer coefficients generated at 8192samples/s) and maximum amplitude greater than 2000000. Filter window 600may be produced by convolving four filter windows including tworectangular filter windows 300 and two rectangular filter windows 400.Consequently, the length of filter window 600 (e.g., 73.33 mS) may equaltwice the length of filter windows 300 (e.g., 40 mS) added to twice thelength of filter window 400 (e.g., 33.33 mS). FIG. 6B depicts afrequency response curve 650 that may correspond to filter window 600.Those familiar with the art may appreciate that the two depicted notchesin the frequency response curve 650 (e.g., one notch at 50 Hz, one notchat 60 Hz) may, for example, correspond to the reciprocal of the lengths(e.g., 1/16.67 mS, 1/20 mS) of rectangular filter windows (e.g., 300,400) that may be convolved to create filter window 600.

Filter window 600 may be considered to correspond to be a fourth orderfilter (e.g., four rectangular or rectangle) filter windows wereconvolved to produce filter window 600) and filter window 500 may beconsidered to correspond to a second order filter. For example, twofirst order filter windows (e.g., rectangle functions) may be convolvedto produce filter window 500. Comparison of frequency response curve 650with frequency response curve 550 shows the benefits (e.g., increasednotch width) associated with using a higher order filter.

On the Fly Generation

The storing of filter windows (e.g., multiple high order filter windows)by conventional methods may prove problematic—particularly inembodiments where storage is costly or limited or inefficient. Forexample, there may be insufficient storage space, in a FieldProgrammable Gate Array (FPGA) with no integrated ROM, to store a filterwindow as a combinatorial function (e.g., as combinational logic) of thediscrete time (sample index) and the desired filter selection. Forexample, filter window 602 depicted in FIG. 6A may consist of more thansix hundred numbers, some of which may have values in the region of2,200,000. Coefficient values of this magnitude may require 21 bits ofstorage space per coefficient. Storing sizable quantities ofcoefficients of this magnitude in RAM may lead to various problems. Forexample, an unacceptable amount of energy may be consumed configuring anFPGA for a new scan (e.g., after power up) using values held in RAM.

According to various embodiments, much less information may be storedand a coefficient generation circuit (e.g., CG 210) may be used toreconstruct filter window coefficients on the fly. Furthermore, the samecoefficient generation circuit may be used to generate filtercoefficient values corresponding to a variety of filter windows and maybe used to produce filter coefficient values for one or more channelsbeing sampled.

In some embodiments, a number of rectangular filter windows (e.g.,rectangular filter windows that may be convolved to generate a desiredfilter window) may be differentiated. The process of differentiation maytransform each rectangle into two delta functions (e.g., one ofmagnitude 1 at time 0, or index 0, and one of magnitude −1 at the end ofthe rectangle). The differentiated rectangles may then be convolved asmany times as desired (e.g., “FO” times, where FO may equal the order ofthe filter), and the resulting convolved function may be composed of(e.g., consist solely of) a few delta functions (e.g., less than orequal to 2^(FO) delta functions) and each one of delta functions may beof limited amplitude (e.g., amplitude less than or equal to 2^(FO-1)).

Accordingly, in some embodiments, a differentiated version of a desiredfilter window of order “FO” may be stored (e.g., as numbers of a sizeless than “FO+1” bits) in a memory (e.g., a memory coupled to CG 210, aROM, a RAM, a NVROM, a Flash memory). Additionally, a majority of thestored numbers may be equal to zero which may be beneficial for storing(e.g., storage space may be reduced, storage methods may be simplified,more cost effective storage solutions may be enabled). Furthermore, adifferentiated filter function may be reconstructed (e.g., generated,produced, calculated) in an efficient manner. For example, in certainembodiments, the function may be reconstructed through a fewcombinatorial functions (e.g., one for each bit of the numbers to bestored) and each function may have few minimum terms to be implemented.In certain embodiments, a zero count (e.g., a number equal to the numberof zeros preceding the delta) may be stored along with the value of eachdelta. For each zero count and delta stored, a counter may count downfrom the zero count value while outputting the value zero. When thecounter reaches a terminal value (e.g., the counter reaches zero) theoutput of the function may be the stored delta value. Then, the nextzero count value may be loaded into the counter and the counter mayoutput zero while counting down from the zero count and then thefunction may output the next stored delta value when the counter reacheszero. Alternatively, the zero count may specify the number of zerossucceeding the delta and a similar counting scheme used.

The efficient storage and reconstruction of delta functions on the fly(e.g., as described above, according to the reception of data samples)may be utilized to generate filter window coefficients in various ways.For example, in some embodiments, the desired coefficients function maybe reconstructed by integrating (e.g., by accumulating) several times(e.g., as many times as the number of rectangles used to create thefilter window, a filter order number of times) the function of deltas.This integration may be performed by using several accumulators arrangedin cascade (e.g., corresponding to ACC[1:P] in FIG. 2). The size of theaccumulators may be tailored to a maximum value they will hold (e.g.,using a priori knowledge) and thus the resources used for theimplementation may be reduced.

FIGS. 7A and 7B

In some embodiments, four rectangular filter windows may be convolved togenerate a filter function that may, for example, resemble filterfunction 750 depicted in FIG. 7B. In some embodiments, the same fourrectangular filter windows may be differentiated and the differentiatedversions of the four rectangular filter windows may convolved (e.g.,with each other) to produce a convoluted function. The convolutedfunction may resemble a function comprising (e.g., consisting of) aplurality of scaled unit delta functions such as, for example, functioncurve 700 depicted in FIG. 7A.

Multiplication of the Generated Constant

In certain systems (e.g., systems with serial ADCs) multiplying a filtercoefficient (e.g., a filter coefficient generated on the fly) by ADCsampled data may be performed by shifting the coefficient value andadding the shifted value to a result accumulator depending if thecurrent bit of ADC serial data being received equates to a binary 1 or a0. Performing multiplication in this manner may be beneficial in variousways (e.g., in terms of cost and/or implementation complexity and/orpower consumption). For example if the ADC (e.g., ADC 114) produces16-bit data and returns data MSB first (as typically found in serialADCs), the generated coefficient may be initially shifted 15 bits to theleft. Thus the shifted coefficient (e.g., the coefficient multiplied by2¹⁵) may be added to the accumulator if the received MSB equals one andthe accumulator may not be updated if the received MSB equals zero.Furthermore, the coefficient may then be shifted one bit right for thenext ADC bit in order to add or not the coefficient multiplied by 2¹⁴depending on the value of bit MSB-1 of the received ADC serial data.

After all the ADC bits have been shifted in the accumulator, theaccumulator may store the values (e.g., current updated values, currentaccumulated values) given by “ACC” in the following equations. Notethat, in the following equations, “ADC[i]” may represent the “ith” bitof the ADC data, “K” may represent the total number of ADC bits (e.g.,8, 16, 24), “ADC[K−1]” may represent the MSB of the ADC data and“ADC[K−1:0]” may represent all the ADC data bits. Note also, that “Coef”may represent the filter coefficient, and ACC′ may represent theoriginal (e.g., pre-updated, starting) value of the accumulator.

${ACC} = {{ACC}^{\prime} + \left\lbrack {\sum\limits_{i = 0}^{i = {K - 1}}{{{ADC}\lbrack i\rbrack}*{Coef}*2^{i}}} \right\rbrack}$This equation may be simplified by factoring the coefficient:—

${ACC} = {{ACC}^{\prime} + {{Coef}*\left\lbrack {\sum\limits_{i = 0}^{i = {K - 1}}{{{ADC}\lbrack i\rbrack}*2^{i}}} \right\rbrack}}$By definition of the binary representation of the ADC value this can befurther simplified to:—ACC=ACC′+Coef*ADC[K−1:0]

Thus, a sequence of shifts and additions (e.g., as previously described)may effectively multiply a received ADC data item by a coefficient valueand add the results of the multiplication to the contents of anaccumulator. In certain embodiments, this may be achieved without usinga register to hold the ADC data item value and/or without using aregister to hold intermediate multiplication results. In one or moreembodiments, a single shifter and single adder may be used and a singleregister may hold the results that may be returned to the user (e.g., atthe end of a scan).

Reutilization of Resources

Various embodiments may provide varying amounts of reuse. For example,in some embodiments, the same accumulator circuitry may be used toperform calculations for different filter windows. In certainembodiments (e.g., in systems supporting multiple channels) once acoefficient value is generated for one channel, that coefficient valueand the multiplier circuit may be used for other channels (e.g., all theother channels associated with a data stream). Such reuse mayeffectively reduce the amount of logic involved in supporting eachchannel. Also, by rotating (e.g., with every new channel acquired) datathrough the result registers (e.g., RACC[M−1:0]) that hold the channelresults, multiple channels may be supported with less circuitry (e.g.,without implementing circuitry to route and/or select data from variouschannel specific result registers). Rotating (e.g., shifting) resultsthrough the result registers may also reduce the amount of additionallogic used to hold and track the results of multiple channels.

Different Operating Modes

Some embodiments may be capable of operating in various modes. Supportof multiple modes may involve flexibly controlling when to generate anew coefficient value and when to rotate accumulated channel data. Someembodiments may support several sample modes via a channel counter and asample counter (which may be viewed as a discrete time index). Certainoperational behaviors may be common to various operating modes. Forexample, the following behaviors may be exhibited in more than oneoperational mode:—a new filter coefficient may be generated when thesample counter changes; the channel result accumulators may be rotatedwhen the channel counter changes; the multiply and add circuit maycalculate a new value when a new ADC sample is received; and a basefunction (function of deltas) may be generated in terms of the samplecounter value. For example, if a base function is generated by countingthe number of zeros between deltas then the zero counter may incrementwhen the sample counter increments.

Some embodiments may support operation in “interleaved mode”. Ininterleaved mode, the supported channels may be processed in a sequence.Each new ADC sample received may correspond to a next channel (e.g., inan ordered set of channels, in a sequence of channels) and, after an ADCsample for the last channel (e.g., a last channel in the ordered set ofchannels) has been received, the sequence may start over with the firstchannel. In certain embodiments, in interleaved mode, the channelcounter may increment on new ADC data and may wrap around after the lastchannel; the sample counter may increment when the channel counter wrapsaround.

Some embodiments may support operation in “non-interleaved mode”. Innon-interleaved mode, all the ADC samples in a first group (e.g., agroup of data samples obtained during a single filter window) maycorrespond to the same channel. Subsequent groups of ADC samples (e.g.,subsequent groups comprising the same number of samples) may correspondto a next channel in a sequence of channels, and so on. In certainembodiments, in non-interleaved mode, the sample counter may incrementon new ADC data and may starts over at the end of a filter window; thechannel counter may increment when the sample channel starts over andthe accumulators may be reset also when the sample channel starts over.

Certain embodiments may support operation in a “burst interleaved mode”.In burst interleaved mode, more than one sample per channel may beacquired for every discrete point in time (e.g., for every filtercoefficient). This may be beneficial (e.g., may increase resolution) incertain embodiments (e.g., in a system with a slow settling channelmultiplexer). In certain embodiments, burst interleaved mode may besupported in a similar fashion to interleaved mode using a burstcounter. In some embodiments, the burst counter may increment on new ADCdata and may reset when a terminal count is reached; the channel countermay increments when the burst counter resets and may wrap around afterthe last channel; and the sample counter may increment when the channelcounter wraps around.

A “phase aligned mode” of operation may also be supported, according tosome embodiments. In phase aligned mode, data samples may be received ina similar (e.g., interleaved) order to interleaved mode or to burstinterleaved modes. However, in phase aligned mode, a new filtercoefficient may be calculated for a new ADC data item (e.g., when thenew data item represents a new data channel). Accordingly, successivedata samples from different channels may be provided with differentcoefficients. For example, two consecutive data samples in a datastream, each sample corresponding to a different data channel, may beprocessed using different coefficients. Phase aligned mode may besupported according to various embodiments. In some embodiments, boththe sample counter and the channel counter may increment their values onnew ADC data (or on a burst of ADC data). Also, the base function (e.g.,the function of deltas) and filter window size may change to take intoaccount the aggregate sample rate instead of the sample rate perchannel. In various embodiments, the channel counter and the samplecounter may behave in a similar fashion to interleaved mode or burstinterleaved mode. However, in phase aligned mode, a new filtercoefficient may be generated on a new channel. And, while base functiongeneration may be similar to interleaved mode or burst interleaved mode,in phase aligned mode, a delta value may be passed only to the firstaccumulator on the first channel of the sample corresponding to thatdelta; a non-delta value (e.g., a zero) may be passed to the firstaccumulator on subsequent samples corresponding to different channels.

Comparing SAR ADCs and Delta-Sigma ADCs

Delta-Sigma ADCs (DSAs) may be used in a variety of applications forvarious purposes. For example, DSAs may commonly be used in lowfrequency applications (e.g., less than 10 Hz, e.g. to integrate outpower line noise). DSAs may also be a good choice for medium bandwidth(20 kHz and below) products since the wide dynamic range of the DSA maymean a programmable gain amplifiers is not required. DSAs may also beused audio and dynamic signal analysis applications [e.g., due to theirexcellent linearity (which may translate into low distortion) and due totheir wide dynamic range]. DSAs may also be used in other applicationareas (e.g., in thermocouple, digital multi-meter, and industrialmeasurement products).

Oversampled SAR ADCs (OSAs) may provide various functional benefits overDSAs. For example, OSAs may allow more flexible designs, so that, forexample, speed and resolution may be gracefully traded for low power.Also, in DC applications for example, an OSA may be able to acquiremultiple channels in the time that a DSA acquires just one channel. Insome systems, a single ADC (and possibly amplifier) may simulate (e.g.,effectively perform the work of) multiple DSAs running simultaneously.However, for all their benefits, OSAs may not replace DSAs in someapplication areas (e.g., in audio, in dynamic signal analysis) sincetoday's DSAs are typically more linear than today's OSAs.

One example of a flexible OSA design may be a battery powered wirelesssensor node design in which speed and/or resolution may be traded offfor lower power (e.g. battery life). In some systems, an oversampled SAR(e.g., 16-bit SAR) may provide better dynamic range than is provided bya non-oversampled SAR. This better dynamic range may mean that aprogrammable gain amplifier is not required, thus reducing the cost andpower of the system. Also, in some systems (e.g., in power-line filteredDC applications) a single multiplexed OSA may produce data at acomparable rate to a similar system which has a DSA per channel.Furthermore, the single multiplexed OSA system may produce data at agreater rate than a similar system which has a multiplexed DSA. In somesystems (e.g., where multiple channels are measured simultaneously),historically expensive (e.g., in dollars and in power)amplifier-and-ADC-per-channel designs may be replaced with a singlemultiplexed OSA design.

FIGS. 8A-8D

FIGS. 8A to 8D may allow noise and filtering characteristics of anexemplary SAR ADC (FIGS. 8A and 8B) to be compared to noise andfiltering characteristics of corresponding exemplary Delta-Sigma ADC(FIGS. 8C and 8D) at various oversampling ratios. FIGS. 8A-Dillustrate—for frequencies up to half the sample rate of the ADC (e.g.,Fs/2)—the impact of changing the oversample ratio and hence the outputrate when the sample rate is held constant.

FIG. 8A includes various waveforms relating filter characteristics andnoise density (on the vertical axis) to frequency (on the horizontalaxis) for an exemplary SAR converter. Curve 802 depicts a first filterresponse curve (e.g., for a first sinc function) corresponding to afirst quantity of samples (e.g., a first output frequency). Curve 804depicts a second filter response curve (e.g., for a second sincfunction) corresponding to a second quantity of samples (e.g., a secondlower output frequency), where the second quantity of samples may begreater than the first quantity of samples and the second outputfrequency may be lower than the first sampling frequency. And, curve 806depicts a third filter response curve (e.g., for a third sinc function)that corresponds to a third quantity of samples (e.g., a third outputfrequency), where the third quantity of samples may be greater than thesecond quantity of samples and the third output frequency may be lowerthan the second output frequency. Lastly, curve 808 depicts noisedensity associated with the SAR converter system, which may be seen tobe approximately constant, at least up to frequency Fs/2 (e.g., half thesampling frequency).

FIG. 8C illustrates how SAR noise density (e.g., noise density curve808) may be shaped by filter response (e.g., by filter response curve802). Curve 810 shows relatively low levels of filtered noise may befound at upper frequency ranges (e.g., at frequencies ranging fromroughly Fs/4 to Fs/2) even when, for example, the first sinc function(that may correspond to a low number of samples and a high outputfrequency) is used.

FIG. 8C depicts various waveforms relating filter characteristics andnoise density (on the vertical axis) to frequency (on the horizontalaxis) for an exemplary delta-sigma converter. In a similar fashion toFIG. 8A, curve 812 depicts a first filter response curve (e.g., for afirst sinc function) corresponding to a first quantity of samples (e.g.,a first output frequency). Curve 814 depicts a second filter responsecurve (e.g., for a second sinc function) corresponding to a secondquantity of samples (e.g., a second lower output frequency), where thesecond quantity of samples may be greater than the first quantity ofsamples and the second output frequency may be lower than the firstoutput frequency. And, curve 816 depicts a third filter response curve(e.g., for a third sinc function) that corresponds to a third quantityof samples (e.g., a third output frequency), where the third quantity ofsamples may be greater than the second quantity of samples and the thirdoutput frequency may be lower than the second output frequency. Lastly,curve 818 depicts noise density associated with the exemplarydelta-sigma converter system where the noise density may be seen to risesignificantly at higher frequencies, e.g., from approximately a quarterof the sampling frequency (e.g., Fs/4) to half the sampling frequency(e.g., Fs/2).

FIG. 8D illustrates how delta-sigma noise density (e.g., noise densitycurve 818) may be shaped by filter response (e.g., by filter responsecurve 812). Curve 820 shows relatively high levels of filtered noise maybe found at higher frequencies (e.g., at frequencies ranging fromroughly Fs/4 to Fs/2) when, for example, the first sinc function (thatmay correspond to a low number of samples and a high output frequency)is used.

A comparison of FIGS. 8B and 8D may indicate that, for similar but smallnumbers of samples (e.g., for similar over-sampling rates, for similarfirst quantities of samples) the total aggregate noise may besignificantly higher in a delta-sigma system than in a corresponding SARsystem.

Taking more samples of data and averaging them may result in a loweroutput rate and lower noise as output rate and noise may be traded offone for the other. The term oversample ratio may be defined as the ratioof the rate at which an ADC samples data versus the rate at whichaveraged values are output by the sampling ADC. If samples are acquiredat a rate of 200,000 per second and every ten samples are averaged andoutput at a rate of 20,000 per second, then the oversampling ratio maybe said to be ten. As illustrated in FIG. 8A, with an SAR ADC, noise maytypically be fairly uniform across its spectrum, so oversamplingtradeoffs may be made smoothly and continuously. Delta Sigma ADCs, onthe other hand, may typically shape their noise so that most of it maybe at higher frequencies, as shown in FIG. 8C. For this reason, highoversample ratios may be used to provide the filtering effect ofaveraging in order to reject this noise. At low oversample ratios thishigh frequency noise may be not be rejected sufficiently well.

FIGS. 9A-9D

FIGS. 9A to 9D allow a comparison of noise density and sample resolutionversus oversampling ratio characteristics of an exemplary SAR ADC (FIGS.9A and 9B) and an exemplary Delta-Sigma ADC (FIGS. 9C and 9D).

FIG. 9A is a chart showing noise density on the vertical axis andfrequency on the horizontal axis. The chart contains a curve 902 ofnoise density versus frequency for an exemplary SAR converter. Asdepicted by curve 902 in FIG. 9A, noise density may remain at a fairlyuniform level across the frequency spectrum of the chart, indicating auseful range of output frequencies up to the oversampling frequency Fs.

FIG. 9B is a chart showing resolution in the form of Effective Number ofBits (ENOB) on the vertical axis and oversampling ratio on thehorizontal axis. The chart features curve 904 which illustrates therelationship between sample resolution (ENOB) and oversampling ratio foran exemplary 16-bit SAR converter. As illustrated by curve 904, theresolution of an SAR ADC may rise linearly with increasing oversamplingratio. According to curve 904, at an oversampling ratio of one, thecorresponding ENOB may be 16-bits.

FIG. 9C is a chart showing noise density on the vertical axis andfrequency on the horizontal axis. The chart contains curve 906 whichillustrates noise density versus frequency for an exemplary Delta-Sigmaconverter. As illustrated by curve 906, the noise density of aDelta-Sigma converter may remain at a fairly uniform level up to auseful output frequency (e.g., “Useful Fout”) after which the noisedensity may rise non-linearly to a new higher level.

FIG. 9D is a chart showing resolution, in the form of ENOB, on thevertical axis and oversampling ratio on the horizontal axis. The chartfeatures curve 908 which illustrates resolution (ENOB) versusoversampling ratio for an exemplary Delta-Sigma converter. Asillustrated by curve 908, the resolution of a Delta-Sigma converter mayrise non-linearly with increasing oversampling ratios. According tocurve 908, at an oversampling ratio of sixteen bits, the correspondingENOB is sixteen.

As depicted in FIG. 9B, the ENOB of an oversampled SAR may smoothly(e.g., linearly) increase with an increase in the number of acquiredsamples (e.g., with an increase in the oversampling ratio). Curve 904indicates that, for an oversampled SAR, one extra bit of resolution maybe obtained for every quadrupling of the oversample ratio. In contrast,a delta-sigma converter may only provide one extra bit of resolution forevery quadrupling of the oversample ratio at higher oversampling ratios.As seen in FIG. 9D, at low oversampling ratios (e.g., less than 16×)resolution may fall steeply as the oversampling ratio falls so that, forexample, there may be a single bit of resolution at an oversamplingratio of one. This steep fall in resolution may be due to the noiseshaping characteristics of Delta-Sigma converters. Since the finaloutput data rate of an ADC may be inversely proportional to itsoversampling ratio, a minimum useful oversample ratio (e.g., ×16) maydefine the maximum useful output rate of a Delta-Sigma converter.

FIGS. 10A-10D

FIGS. 10A to 10D allow a comparison of resolution versus power andresolution versus output data rate for an exemplary oversampled SAR ADC(FIGS. 10A and 10B) and an exemplary Delta-Sigma ADC (FIGS. 10C and10D). Since taking each data sample may require additional power to beconsumed (e.g., by sampling circuitry) the oversampling ratio may beindicative of power consumption. And, for a given sampling frequency,the oversampling rate may be inversely proportional to the output datarate.

FIG. 10A is a chart with resolution (e.g., ENOB) on the vertical axisand power (oversampling ratio) on the horizontal axis. In FIG. 10A,curve 1002 illustrates the relationship between resolution and power foran exemplary oversampled SAR converter at a given output rate. Asillustrated by curve 1002, for example, the resolution of a SARconverter may rise linearly as the oversampling ratio (e.g., power) isincreased.

FIG. 10B is a chart with resolution (e.g., ENOB) on the vertical axisand output data rate on the horizontal axis. The output rate may bemeasured in relative terms so that, for example, 256 may indicate anoutput rate 256 times an output rate of 1. Curve 1004 depicts therelationship between resolution and output rate for an exemplaryoversampled SAR converter being oversampled at a given oversample rate.As illustrated by curve 1004, for example, the resolution of a SARconverter may fall linearly with increasing output rate (e.g., for afixed sampling frequency).

FIG. 10C is a chart with resolution (ENOB) on the vertical axis andoversampling ratio on the horizontal axis. Curve 1006 illustrates therelationship between resolution and oversampling ratio for an exemplaryDelta-Sigma converter at a given output rate. As illustrated by curve1006, for example, the resolution of a Delta-Sigma converter may risenon-linearly as power consumption (e.g., the oversampling ratio)increases.

FIG. 10D is a chart with resolution (e.g., ENOB) on the vertical axisand output rate on the horizontal axis. Curve 1008 illustrates therelationship between sample resolution and output rate for an exemplaryDelta-Sigma converter at a given oversample rate. As depicted by curve1008, for example, the resolution of a Delta-sigma converter may fall ina non-linear fashion with increasing output rate.

FIGS. 10A and 10C illustrate that, for a given output rate, theoversampling ratio may be adjusted by increasing the sample rate whichmay increase ADC resolution (but which may also increase converterpower). Consequently, converter resolution and power may be traded offfor each other. However, the minimum useful oversample ratio of aDelta-Sigma converter may limit the ability to use low power settings.For example, a SAR converter (e.g., the exemplary SAR of FIG. 10A) mayoperate using a 4× oversampling ratio (e.g. to achieve power savingsover a 10× oversampling ratio) while providing 17 bits of resolution.However, a Delta-Sigma converter (e.g., the exemplary SAR converter ofFIG. 10C) may only be able to provide 4 bits of resolution whileoperating in a 4× oversampling mode, which may be insufficient.

FIGS. 10B and 10D illustrate that, for a given sample rate, adjustmentsto the oversampling ratio may change the output rate but may keep thepower constant. Consequently, converter resolution and output rate maybe traded off for each other. However, the minimum useful oversampleratio of a Delta-Sigma converter may limit on how fast the output ratecan go. For example, the oversampling rate of a SAR converter (e.g., theexemplary SAR converter of FIG. 10B) may be reduced so that theresolution fall from twenty bits to 16 bits, and this may increase theoutput rate by a factor of 256. However, the steep non-linear fall offin output rate shown in curve 1008 indicates that a Delta-Sigmaconverter (e.g., the exemplary Delta-Sigma converter of FIG. 10D) maynot increase the output rate by such a factor, even with a greater dropin resolution.

FIGS. 11A and 11B

FIGS. 11A and 11B show how sampling (e.g., oversampling) of multiplechannels (e.g., four channels) may be performed using a multiplexedDelta-Sigma converter (FIG. 11A) and by using a multiplexed SARconverter (FIG. 11B). For ease of comparison both figures have similarintegration period lengths.

In FIG. 11A, four successive integration periods are shown. In eachintegration period one of the four channels may be sampled by aDelta-Sigma converter. For example, channel zero may be acquired duringintegration period 1102, channel one may be acquired during integrationperiod 1104, channel two may be acquired during integration period 1106and channel three may be acquired during integration period 1108.Further integration periods (not depicted) may be used to acquire thesame four channels (e.g., in a loop) or acquire additional channels(e.g., also in a loop). Note that each integration period (e.g., 1102,1104, 1106, 1108 etc.) may involve the taking of multiple samples (e.g.oversampling) by the Delta-Sigma converter in accordance with thetypical use of Delta-Sigma converters.

In FIG. 11B, four overlapping integration periods are shown. In eachintegration period one of the four channels may be sampled by anoversampling multiplexed SAR converter. For example, channel zero may beacquired during integration period 1110, channel one may be acquiredduring integration period 1112, channel two may be acquired duringintegration period 1114 and channel three may be acquired duringintegration period 1116. Note that these integration periods may runconcurrently (e.g., significantly overlapping) and that after a sampleis taken for a first channel (e.g., channel 1) the next sample may betaken for a second channel (e.g., for channel 2) and so on until afterthe last channel (e.g., the fourth channel, channel 3) the next samplemay be taken again from the first channel (e.g., channel 1).

By interleaving the samples of multiple channels the multiplexed-SARbased design may output multiple channels of power-line filtered data ina single integration period. In contrast, a multiplexed Delta-Sigmaconverter may only output one channel of filtered data out in anintegration period. For example, if an integration period of 20 ms ischosen to provide 50 Hz notches, it may take 80 ms to obtain fourchannels of data from a multiplexed Delta-Sigma converter, while amultiplexed SAR-based design may output all those channels in 20 ms.

In designs where the amplifiers and sensors may be powered only duringthe acquisitions, reducing acquisition time may reduce powerconsumption. Accordingly, a SAR-based design may be used to sample(e.g., obtain, process) a similar quantity of data at lower power, orsample a greater data at similar power, as compared to a Delta-Sigmabased design. As illustrated in FIGS. 11A and 11B, for example, aSAR-based design may be able to produce four times more data in asimilar time and for similar power as a Delta-Sigma based design (e.g.,by repeating the interleaved measurement every 20 ms). Also, theSAR-based design may be able to output a similar quantity of data forless power than a Delta-Sigma based design (e.g., if it powers down for60 ms after each 20 ms acquisition).

FIGS. 12A and 12B

FIGS. 12A and 12B illustrate two schemes for sampling multiplexedchannels.

FIG. 12A depicts four multiplexed channels that may be coupled to acommon amplifier, the output of which may feed into a SAR converter. Thedepicted channels may be channel zero 1202, channel one 1204, channeltwo 1206 and channel three 1208. These four channels may be multiplexedonto a common output by multiplexer 1210 and the output of multiplexer1210 may be coupled to the input of amplifier 1212. The output ofamplifier 1212 may feed into SAR converter 1214.

Curve 1216 of FIG. 12A illustrates the signal level (e.g., voltagelevel) at the output of amplifier 1212 over a period of time. Points1218, 1220, 1222 and 1224 on curve 1216 may indicate the locations ofsamples taken by SAR converter 1214. Multiplexer 1210 may regularlyswitch from channel to channel in sequence so that samples of eachchannel may be taken by SAR converter 1214. When multiplexer 1212switches to a new channel (e.g., from channel zero to channel one), anew sample period (e.g., 1230, 1232, 1234, 1236) may begin and theoutput waveform (e.g., 1216) of amplifier 1212 may abruptly change to anew level corresponding to signal on the currently selected channel.After some time (e.g., the settling period on the amplifier), theamplifier output may stabilize and a sample may be taken. Sampling theamplifier output before the output stabilizes may result in lessaccurate (e.g., noisy) data and so it may be beneficial to waitsufficiently long for the output to stabilize. After a sample is taken,the corresponding sample period may end and the multiplexer may select anew input and a new sample period may begin. Again, the output of theamplifier may change abruptly.

A potential drawback to interleaving measurements by multiplexing into aSAR converter is that the settling time of an amplifier (e.g., theamplifier that drives the SAR converter) may determine the speed atwhich the SAR converter may sample. For example, to enable high speedsampling a designer may select an amplifier with a correspondingly fastsettling time. An amplifier with a fast settling time may be moreexpensive and consume more power than a similar, but slower, amplifier.One option may be to put an amplifier per channel in front of themultiplexer; this option may cost more than using a single fastamplifier but may provide benefits in terms of power consumption.

Another solution may involve using a single amplifier. However, ratherthan selecting an amplifier which is sufficiently powerful to settle atthe full sampling rate of the ADC, a lower power amplifier is selected.Since multiple readings (e.g., samples) may be averaged, an ADC may beoperated in bursts (e.g., burst of samples may be taken). For example,in some multi-channel, multiplexed embodiments, the system may waitsufficiently long (e.g., after selecting a new input channel) for theoutput of the amplifier (e.g., the amplifier coupled to the multiplexer)to settle and then a burst of samples may be taken at the full rate ofthe ADC. The multiplexer may then switch to another channel and repeatthe process.

FIG. 12B illustrates the burst sampling process according to variousembodiments. Curve 1256 depicts the signal level (e.g., voltage level)at the output of a post-multiplexer amplifier (e.g., amplifier 1212)over time. Curve 1256 is of similar shape to curve 1216 thus aidingcomparison of the two differing approaches. In some embodiments, a burstof samples may be taken after each change of channel. For example, oncurve 1256, a first burst of samples 1258 may be taken for a firstchannel (e.g., channel zero), a second burst of samples 1260 may betaken for a second channel (e.g., channel one), a third burst of samples1262 may be taken for a third channel (e.g., channel two) and a fourthburst of samples 1264 may be taken for a fourth channel (e.g., channelthree). Comparing curve 1216 (FIG. 12A) and curve 1256 (FIG. 12B),single sample 1218 on curve 1216 may correspond to burst samples 1258 oncurve 1256, single sample 1220 on curve 1216 may correspond to burstsamples 1260 on curve 1256, single sample 1222 on curve 1216 maycorrespond to burst samples 1262 on curve 1256, and single sample 1224on curve 1216 may correspond to burst samples 1264 on curve 1256.

Some multi-channel ADC systems (e.g., ADC systems with a single SAR),may switch channels, wait for the amplifier to settle, take a singlesample, and repeat. But, in some situations (e.g. when the amplifiersettling time larger than the ADC sampling time) many more samples maybe taken per unit time by employing burst sampling (e.g., as describedabove). In certain embodiments (e.g., in systems that oversample andaverage SAR readings) acquiring more samples per unit time may providebetter performance, and an unusual timing relationship between thesamples of burst mode may not be important.

FIGS. 13A and 13B

FIGS. 13A and 13B illustrate the relationship between the average timesof successive measurements in a multiplexed multi-channel system. FIG.13A illustrates the relationship between the average times of successivemeasurements in a multiplexed, Delta-Sigma system. FIG. 13B illustratesthe relationship between the average times of successive measurements ina multiplexed SAR system.

FIG. 13A depicts four successive acquisition periods that may be used toacquire four multiplexed channels in a Delta-Sigma based system. Duringacquisition period 1302 channel zero data may be sampled, duringacquisition period 1304 channel one data may be sampled, duringacquisition period 1306 channel two data may be sampled and duringacquisition period 1308 channel three data may be sampled. As previouslydiscussed, a Delta-Sigma converter may typically sample multiple timesduring an integration period (e.g., 16 times, 64 times) and the resultsof the multiple samples may be averaged. Since the multiple samples maybe taken at regular intervals during an acquisition period, the averagetime of measurement for the samples taken during an acquisition periodmay be approximately the time at the middle of the acquisition period.As depicted in FIG. 13A, the average time of measurement of successivemeasurements in a multiplexed Delta-Sigma system may differ by theintegration period (e.g., acquisition period). So, for example, for anacquisition period of 32 mS, the average time of measurement for achannel zero (e.g., Ch. 0) measurement may be 32 mS earlier than theaverage time of measurement for a successive channel one (e.g., Ch. 1)measurement.

FIG. 13B depicts four successive, interleaved acquisition periods thatmay be used to acquire four multiplexed channels in some embodiments(e.g., some SAR based systems). During acquisition period 1310 channelzero data may be sampled, during acquisition period 1312 channel onedata may be sampled, during acquisition period 1314 channel two data maybe sampled and during acquisition period 1316 channel three data may besampled. As depicted in FIG. 13B the acquisition periods may be largelyoverlapped (e.g., offset by a sampling period), interleaved (e.g., eachsuccessive sample is taken from a next channel) and run concurrently(e.g., not in series). As previously discussed, a SAR converter maysample multiple times during an acquisition period (e.g., 16 times, 64times) and the results of the multiple samples may be combined (e.g.,averaged, weighted, computed etc.) Since the multiple samples may betaken at regular intervals during an acquisition period (e.g., duringacquisition period 1310 etc.), the average time of measurement for theaveraged samples may be approximately the time at the middle of theacquisition period. As depicted in FIG. 13B, since the acquisitionperiods for the multiple channels may be largely overlapped (e.g., withrelatively small offset) the average time of measurement of successiveaverage measurements in a multiplexed SAR system may differ by arelatively small amount (e.g., the sample period of the converter). So,for example, if the acquisition period is 32 mS and sixteen samples aretaken during the acquisition period, the average time of measurement fora channel one measurement may be 2 mS earlier than the average time ofmeasurement for a successive channel two measurement.

The interleaved and oversampled SAR approach may obtain a complete setof data samples from all the channels within a single integrationperiod. This may provide the benefit that the averaged data, for eachchannel sampled, represents the value of that channel's signal atapproximately the same time as the other channels. In contrast, amultiplexed delta-sigma approach may results in each channel providingits data after an integration period, so the measurements of thedifferent channels do not represent those channels' values at the samepoint in time. In some embodiments, the time delay between measurementsin an interleaved SAR system may correspond to the time taken by amultiplexer to switch from channel to channel. Since the switching timeof a multiplexer may be much smaller than an integration period this mayprovide a substantial improvement to the inter-channel phase delay ofthe measurements.

FIGS. 14A and 14B

FIGS. 14A and 14B illustrates alternative schemes for applying weightingfunctions to multiplexed channels. FIG. 14A illustrates a scheme inwhich, for example, the same weighting function may be applied to allchannels. FIG. 14B illustrates an alternative scheme in which theweighting function may be changed after each change in channel

FIG. 14A illustrates a scheme in which the same weighting function maybe applied to each one of the multiplexed channels. FIG. 14A depictsthirty-six data samples arranged as four sets of nine samples. Eachsample is indicated by a circle that is shaded (according to theprovided legend) to indicate a corresponding channel. Samples associatedwith the same channel are connected by dashed lines. On FIG. 14A, timemay increase from left to right and filter values may increase frombottom to top. The position of each sample (and the connecting dashedlines) is intended to convey the relative time of the sample and therelative value of the filter coefficient applied to the sample. Forexample, the first four samples (e.g., of an integration period) may beacquired in the following order, channel 0 sample 1402A, channel 1sample 1404A, channel 2 sample 1406A and channel 3 sample 1408A. Thesefour samples (e.g., 1402A-1408A) are depicted at a similar height inFIG. 14A to indicate they may be filtered using a similar (e.g., thesame), coefficient value. After these four samples are acquired anotherfour samples may be taken. For example, four more samples may beacquired in the following order, channel 0 sample 1410A, channel 1sample 1412A, channel 2 sample 1414A and channel 3 sample 1414A. Thesenext four samples are also depicted at a similar height in FIG. 14A toindicate that they too may be filtered using a similar (e.g., the same),coefficient value. However, as indicated by their relative verticalpositions, the filter coefficient value used for samples 1410-1416 maybe larger than the filter coefficient value used for sample 1402-1408.The sampling and filter procedure may continue as described for allthirty six data samples.

Those skilled in the art will appreciate that FIG. 14A may illustratethe sampling of four channels and the application of a similar (e.g.,identical) triangular filter window (e.g., weighting function) to eachof the channels (e.g., in an interleaved, multiplexed SAR system). Sincethe weighting function may be the same for all the channels (e.g.,channels 0 through 3) and since each sample (e.g., 1404A) may have atemporal offset (e.g., by a multiplexer delay, by a sampling delay, by aamplifier settling time delay, by a combination of small delays) fromneighboring samples (e.g., 1402A, 1406A) so the effective sample time ofeach group (e.g., a single integration period's worth of samples for onechannel) may be slightly offset. Thus the data output measurement (e.g.,the average measurement after filtering) for each channel may beconsidered offset from neighboring channels, although perhaps onlyslightly.

However, the output measurements for the channels may be effectivelyphase aligned by, for example, the application of an incrementingweighting function. FIG. 14B illustrates a scheme in which anincrementing weighting function may be applied to multiplexed channels.As in FIG. 14A, FIG. 14B depicts thirty-six data samples arranged asfour sets of nine samples. Again, in similar fashion to FIG. 14A, eachsample is indicated by a circle that is shaded (according to theprovided legend) to indicate a corresponding channel. Samples associatedwith the same channel are connected by dashed lines (which may nowsubstantially overlap). As with FIG. 14A, time may increase from left toright and filter values may increase from bottom to top. The position ofeach sample (and the connecting dashed lines) is intended to convey therelative time of the sample and the relative value of the filtercoefficient applied to the sample. For ease of comparison, samples arenumbered similarly to FIG. 14A but, in FIG. 14B, the sample numbers havea “B” postfix. So, in FIG. 14B, the first four samples (e.g., of anintegration period) may be acquired in the following order, channel 0sample 1402B, channel 1 sample 1404B, channel 2 sample 1406B and channel3 sample 1408B. These four samples (e.g., 1402B-1408B) are depicted withsuccessively increasing heights in FIG. 14B indicating they may befiltered using an incrementally changing coefficient value (e.g., thefilter coefficient may change for each sample). After these four samplesare acquired another four samples may be taken in a similar fashion. Forexample, four more samples may be acquired in the following order,channel 0 sample 1410B, channel 1 sample 1412B, channel 2 sample 1414Band channel 3 sample 1414B. These next four samples are also depicted atsuccessively increasing heights indicating that they too may be filteredusing an incrementally changing coefficient values. The same ordering ofsamples and the same relationship between each sample and its respectivefilter coefficient (e.g., as described for the first eight samples) mayapply to all thirty six data samples depicted in FIG. 14B.

FIGS. 14A and 14B allow comparison of two filtering approaches. FIG. 14Aillustrates a first scheme in which, for example, a similar (e.g.,identical, same) weighting function may be applied to all channels. Inthis first scheme, the weighting function may be changed after each scanof all channels (e.g., after four samples, after sample 1408A, aftersample 1416A). FIG. 14B illustrates a second scheme in which, forexample, an incrementally changing weighting function may be applied toeach successive sample. In this second scheme, the weighting functionmay be changed after each change in channel (e.g., after one sample,after samples 1402B, 1404B, 1406B etc). This approach may effectivelyput all samples (e.g., all samples taken within an integration period,all samples from all channels) on a master filter window which mayeffectively phase align the samples from each channel. This phasealignment may be accomplished when using different (e.g., 4^(th) order,triangle) filter windows for each channel.

An incrementing weighting function scheme (e.g., as illustrated in FIG.14B) may be used in some embodiments to reduce (e.g., minimize,eliminate, mitigate) even the small residual apparent time delay betweenoutput data measurements (e.g., the difference in effective samplingtimes shown in FIG. 14A). By incrementing through the weighting functionvalues after every channel change, rather than after every scan throughthe channels, data samples may be weighted as if they were on a masterwindow that has the same effective time of sampling for every channel.

With an incrementing weighting function, each channel may see a slightlydifferent filter window and these filter windows may have anon-symmetric shape. Although the filter windows may be unusual (e.g.,be non-symmetric), or may appear unusual, they may be easy to implementand may thus provide a suitable way to remove residual phase delay.However, the incrementing weighting function may involve more filtervalues and the filter values may be of higher resolution. This may leadto an increase in the number of and size of registers used to holdwindow filter values. For example, the incrementing weighting functionof FIG. 14B may involve four times the number of filter coefficients(and two extra bits of resolution) as the standard weighting function ofFIG. 14A. A benefit of using an incremental weighting function may bethat measurements may appear to have been taken simultaneously. This issomething that previously may have been accomplished by using an ADC andamplifier per channel, which may substantially increase cost.

FIGS. 15A through 15E

FIGS. 15A through 15E illustrate the operation of multiply accumulator250 according to various embodiments. FIG. 15A depicts portion 1500 ofmultiply accumulator 250 circuitry according to one or more embodiments.A comparison of FIG. 15A and the multiply accumulator 250 of FIG. 2 mayreveal some differences in the components (and connections betweencomponents) but the operation of the two embodiments may besubstantially similar. The number of accumulator registers (e.g., “M”,RACC[M−1:0]) in portion 1500 may be 4. The depicted portion 1500 mayinclude result accumulator registers RACC[3] 1501, RACC[2] 1502, RACC[1]1503, RACC[0] 1504, adder 1505, multiplexer 1506 and shifter 1507. Indepicted portion 1500, data held in RACC[3] 1501 (e.g., data previouslytransferred from RACC[0] 1504) may be supplied to adder 1505 viaconnection 1508. Also, data held in RACC[0] 1504 may be transferred toregister RACC[3] 1501 via multiplexer 1506 and connection 1509.

FIG. 15B illustrates a plurality of samples 1512 that may be processedusing NRF 112, where NRF 112 may include multiply accumulator 250 andwhere multiply accumulator 250 may include portion 1500. The pluralityof samples 1512 may include a plurality of sample sequences such as, forexample, sample sequence 1514 and sample sequence 1516. The plurality ofsample sequences may be considered to be a succession (e.g., a sequence,a stream) of sample sequences where, for example, sample sequence 1514may be considered an earlier sample sequence than sample sequence 1516and sample sequence 1516 may be considered a later sample sequence thansample sequence 1514. Also, where sample sequence 1516 and samplesequence 1514 are neighboring sample sequences (e.g., there are nosample sequences falling between 1514 and 1516) then sample sequence1514 may be considered to precede (e.g., immediately precede, precede inthe succession of sample sequences 1512) sample sequence 1516 and samplesequence 1516 may be considered to succeed (e.g., immediately succeed,succeed in the succession of sample sequences 1512) sample sequence1514.

Each sample sequence may include a similar (e.g., the same) number ofsamples. For example, sample sequence 1514 may include four samples(sample “A0” 1520, sample “B0” 1521, sample “C0” 1522 and sample “D0”1523) and sample sequence 1516 may also include four samples (sample“A1” 1524, sample “B1” 1525, sample “C1” 1526 and sample “D1” 1527). Theplurality of sample sequences may include a large number of samplesequences and the sample sequences may be generated in real time (e.g.,generated continuously in real-time, generated regularly for an extendedperiod).

Many (e.g., all, a majority of) sample sequences (e.g., 1516, 1514) inthe plurality of sample sequences 1512 may be ordered (e.g., samples mayarranged within the sequence) according to a common format. For example,in some embodiments, each sample in a sample sequence may correspond toa channel (e.g., one of the channels connected to analog FE 116). Forexample, sample “A0” 1520 may belong to a channel designated “A” (e.g.,channel 7), sample “B0” 1521 may belong to (e.g. come from) a channeldesignated “B” (e.g., channel 4), sample “C0” 1522 may belong to achannel designated “C” (e.g., channel 0) and sample “D0” 1523 may belongto a channel designated “D” (e.g., channel 2).

In some embodiments, each sample in a sample sequence may correspond toa different channel in set of channels and the common format maycorrespond to an ordered set of channels. For example, as depicted inFIG. 15B, a number of sample sequences (e.g., all sample sequences,sample sequences 1514, 1516) may be ordered according to a common formatthat corresponds to an ordered set of channels (e.g., channel “A” first,channel “B” second, channel “C” third and channel “D” fourth). Forexample, samples “A0” 1520, “A1” 1524 and “A2” 1528 may respectivelyrepresent first, second and third samples from channel “A”, samples “B0”1521 and “B1” 1525 may respectively represent first and second samplesfrom channel “B”, samples “C0” 1522 and “C1” 1526 may respectivelyrepresent first and second samples from channel “C”, and samples “D0”1523 and “D1” 1527 may respectively represent first and second samplesfrom channel “D”.

In some embodiments, samples occupying the same position withinrespective sample sequence (e.g., sample A0 1520 occupying firstposition within sample sequence 1514 and sample A1 1524 occupying firstposition within sample sequence 1516) may form a series (e.g., asequence, a succession) of samples from common channel (e.g., channel“A”). Furthermore, samples occupying the same position (e.g., “C0” 1522,“C1” 1526) within successive sample sequences (e.g., samples sequences1514 and 1516) may be successive samples from a channel (e.g.,successive samples from channel “C”). The samples depicted in FIG. 15Bare shaded and named (e.g., by the first letter of the sample name) toindicate, for each respective sample, a corresponding channel. Forexample, samples from channel “A” are cross-shaded and are named “A$”where “$” may represent a relative position within a series of samplesfrom channel “A”; samples from channel “B” are shaded white and arenamed “B$” where “5” may represent a relative position within a seriesof samples from channel “B”; samples from channel “C” are diagonallyshaded and are named “C$” where “$” may represent a relative positionwithin a series of samples from channel “C”; and finally, samples fromchannel “D” are shaded solid grey and are named “D$” where “$” mayrepresent a relative position within a series of samples from channel“D”.

FIG. 15C depicts a table 1530 that illustrates the changing contents ofaccumulator registers (e.g., RACC[3:0] of FIG. 15A) and the movement ofdata between accumulator registers (e.g., between registers RACC[3]1501, RACC[2] 1502, RACC[1] 1503 and RACC[0] 1504) during the processingof the plurality of data samples 1512 according to various embodiments(e.g., embodiments that may correspond to portion 1500).

Cells in table 1530 are shaded according to the contents of theindividual cell. Cells are shaded in a similar fashion to the pluralityof samples 1512. For example, cells that may be associated with channel“A” or that may be associated with a sample corresponding to channel “A”(e.g., sample “A0” 1520 or sample “A1” 1524) are cross-hatch shaded.Also, cells that may be associated with channel “C” or that may beassociated with a sample corresponding to channel “C” (e.g., sample “C0”1522 or sample “C1” 1526) are diagonally shaded.

Table 1530 has four columns (e.g., 1532, 1534, 1536 and 1538) where eachcolumn may display the contents of a respective accumulator register.So, in table 1530, column 1538 may display the contents of the RACC[3]register 1501, column 1536 may display the contents of the RACC[2]register 1502, column 1534 may display the contents of the RACC[l]register 1503 and column 1532 may display the contents of the contentsof the RACC[0] register 1504. Table 1530 is also organized by rows andeach row may display the contents of the four RACC registers atsuccessive points during the processing of samples 1512. The top row1541 of table 1530 may depict RACC[3:0] register contents prior toprocessing sample sequence 1514 and the bottom row 1557 may depictRACC[3:0] register contents subsequent to processing sample sequence1516.

In table 1530, top row 1541 may depict RACC[3:0] contents afterinitialization values have been stored in registers. Initializationvalues may be stored in each register to correspond to a channel. Forexample, an initialization value “INA” corresponding to channel “A” maybe stored in RACC[3] register 1501 and an initialization value “IND”corresponding to channel “D” may be stored in RACC[2] register 1502 andsimilarly for initialization values “INC” and “INB”. The initializationvalues “INA”, “INB”, “INC” and “IND” may be various values (e.g., may bethe same value, may be zero, may correspond to previous samples etc.)The remaining rows in table 1530 may be partitioned into groups of tworows (e.g., rows 1542 and 1543, rows 1544 and 1545), and each group oftwo rows may correspond to a sample of the plurality of samples 1512.

The top row of each group of two rows may depict accumulator registercontents after a sample has been processed and a corresponding resulthas been stored. For example, row 1542 “A0 store” may depict thecontents of accumulator registers RACC[3:0] after sample “A0” 1520 hasbeen processed and corresponding result “A0R” has been stored.Similarly, row 1554 “C1 store” may depict the contents of accumulatorregisters RACC[3:0] after sample “C1” has been processed andcorresponding result “C1R” has been stored. In table 1530, the result ofprocessing a sample “X#” (where X may be “A”, “B”, “C” or “D” and “#”may be “0”, “1”) of the plurality of samples 1512, may be designated“X#R”.

The bottom row of each group of two rows may depict accumulator registercontents after the contents of accumulator registers RACC[3:0] have beenshifted. For example, row 1543 “A0 shift” may depict the contents ofaccumulator registers RACC[3:0] after the register contents shown in row1542 “A0 store” have been shifted. Similarly, row 1555 “C1 shift” maydepict the contents of accumulator registers RACC[3:0] after theregister contents shown in row 1554 “C1 store” have been shifted. Asdepicted in FIG. 15C, in some embodiments, after each successive samplein each sample sequence is processed, the contents of the resultaccumulator registers may be shifted.

In some embodiments, (e.g., as depicted in FIGS. 15A, 15B and 15C), thenumber of accumulator registers (e.g., RACC[3:0]) may match the numberof samples in a sample sequence, e.g., 4), the contents of theaccumulator registers (e.g., RACC[3:0]) may be shifted once per resultstore operation (e.g., after each result store operation, before eachstore operation), the result accumulators may be coupled in series(e.g., in sequence) and an output of the trailing (e.g., last in series)accumulator register (e.g., RACC[0]) may be coupled to an input of theleading (e.g., first in series) accumulator register (e.g., RACC[3]) sothat result data within the accumulator registers (e.g., results “A0R”,“B0R” etc.) may be rotated through the accumulator registers. In someembodiments, the contents of the result accumulator registers may berotated in sequence with the order of samples in sample sequences beingprocessed (e.g., sample sequence 1514, 1516) in such a way that, foreach sample being processed, result data corresponding to a precedingsample (or preceding samples) from the same channel may be stored in thefirst accumulator register (e.g., RACC[3], the accumulator registercoupled, e.g., via 1508, to adder 1505. This may allow, for example,results for the current sample to be combined (e.g., accumulated) withone or more previous results (e.g., previous results from the samechannel).

Shifting (e.g. rotating) the contents of accumulator registers RACC[3:0]in sequence with the successive processing of samples from the pluralityof samples 1512 may be observed in FIG. 15C. As shown in the row 1541,RACC[3] 1501 may hold “INA” (e.g., an initialization value for channel“A”). The value “INA” may be added (e.g., in adder 1505) to anothervalue (e.g., a value calculated for sample “A0” 1520) to produce aresulting accumulated value (e.g., “A0R”) that may be stored in RACC[3]1501 (as depicted in row 1542), overwriting value “INA”. After the storeoperation of row 1542, result data may be rotated through RACC[3:0] sothat, for example, RACC[3] 1501 may now hold the value “INB” as depictedin row 1543.

The value “INB” (e.g. an initialization value for channel B) held inRACC[3] 1501 may be supplied (e.g., to adder 1505 via connection 1508)to produce, for example, an accumulated value “B0R” for sample “B0”1521. And, as depicted in row 1544, accumulated value “B0R” may bestored into RACC[3] 1501 overwriting “INB”. Then, the contents of eachregister in the sequence of result accumulator registers may be shiftedto the next successive register in the sequence, as depicted in tow 1545for example.

A resulting value “C0R” corresponding to sample “C0” 1522 may besimilarly generated and stored (e.g., as illustrated in row 1546),followed by a rotation of stored data (e.g., as illustrated in row1547). Similarly, for sample “D0” 1523, a resulting value “D0R” may begenerated and stored (e.g., as illustrated in row 1548), followed by arotation of stored data (e.g., as illustrated in row 1549). By row 1549,all the initialization data (e.g., channel initialization data “INA,IND, INC, INB”) stored in the accumulator registers RACC[3:0] may beoverwritten with resulting data (e.g., “A0R, D0R, C0R, B0R”)corresponding to samples from sample sequence 1514.

After sample D0 has been processed, and resulting data shifted (e.g. row1549) the first sample of next sample sequence (e.g., sample “A1” 1524)may be processed. As shown in row 1549, RACC[3] 1501 may hold the value“A0R” the value resulting from processing sample A0 1520. The value“A0R” may be added (e.g., in adder 1505) to a value calculated forsample “A1” 1524 to produce a resulting accumulated value (e.g., “A1R”)that may be stored in RACC[3] 1501 (as depicted in row 1550),overwriting value “A0R”. After the store operation of row 1550, resultdata may be rotated through RACC[3:0] so that, for example, RACC[3] 1501may now hold the value “B0R” as depicted in row 1551. The value “B0R”(e.g., the value resulting from the processing of sample “B0”) held inRACC[3] 1501 may be supplied (e.g., to adder 1505 via connection 1508)to produce, for example, an accumulated value “B1R” for sample “B1”1525, and accumulated value “B1R” may be stored (e.g., as depicted inrow 1552) into RACC[3] 1501 overwriting “B0R”. After the store operationof row 1552, result data may be rotated through RACC[3:0] so that, forexample, RACC[3] 1501 may now hold the value “C0R” as depicted in row1553. A resulting value “C1R” corresponding to sample “C1” 1526 may besimilarly generated and stored (e.g., as illustrated in row 1554),followed by a rotation of stored data (e.g., as illustrated in row1555). Similarly, for sample “D1” 1527, a resulting value “D1R” may begenerated and stored (e.g., as illustrated in row 1556), followed by arotation of stored data (e.g., as illustrated in row 1557). By row 1557,all the resulting data corresponding to sample sequence 1514 (e.g.,resulting data “A0R, D0R, C0R, B0R”) held in the accumulator registersRACC[3:0] may be overwritten with resulting data (e.g., “A1R, D1R, C1R,B1R”) corresponding to samples from sample sequence 1516. In such amanner, for each channel of a plurality of channels, resultscorresponding to successive samples from the channel may be accumulatedtogether.

In one sense, coefficient generator 210 and multiply accumulator (MAC)250 operate together to multiply a coefficient with a serial ADC sampleon the fly. In other words, the ADC sample bits may be used as they arereceived serially, without a need for storing or holding those bits, toenable/disable an accumulator register that may add to itself the valueof a shifted constant. This may effectively implement a multiply-and-addoperation by the time all the ADC sample bits have been received, andmay therefore save the cost of holding the intermediate value of the ADCsample and the intermediate value of the product of the ADC value andthe filter coefficient. As shown in FIG. 2, MAC circuitry 250 may bedesigned for multiple channels by having various registers connected ina circular arrangement (one embodiment for 4 channels is shown in FIG.15A). The first register may operate to calculate a new intermediatevalue (a current effective sample) for a given channel, and all thevalues in the sequence of registers may be rotated to have the firstregister hold the accumulated value for the next channel in order tocalculate the new intermediate value for that other channel, and so onfor all the channels. This may be performed as many times as the numberof samples to be processed. By performing the operation in thismanner—in contrast to using each channel register to provide data to theMAC circuitry and store the result of the MAC circuitry for thatchannel—there may be no need for a M×N-to-N multiplexer, where M is thenumber of channels and N is the number of bits of the accumulator, withN×M referring to the product of M and N, i.e.“M times N”, and to selectwhich register is coupled to the MAC circuitry at any given time.Instead, Shifter 254 and Adder 260—referring again to FIG. 2—togetherwith any associated control signals designed to enable and synchronizethe operation of Shifter 254 and Adder 260, may be used to perform asequence of additions that involve all the registers or accumulators(e.g. RACC[M−1] to RACC[0]), by introducing multiplexer 262, which maybe a 2×N-to-N multiplexer instead of a M×N-to-N multiplexer. Asmentioned above, FIG. 15A shows one embodiment where the number ofchannels (the number of registers, M) equals 4.

FIG. 15D depicts an alternative embodiment 1560 of a portion of multiplyaccumulator 250 circuitry. As depicted, the number of accumulatorregisters (e.g., “M”, RACC[M−1:0]) in embodiment 1560 may be 5. Acomparison of FIG. 15D and the multiply accumulator 250 of FIG. 2 mayreveal some differences in the components (and connections betweencomponents) but the two embodiments may be operated in a similarfashion. The depicted embodiment 1560 may include shifter 1566, adder1567, multiplexer 1568 and result accumulators RACC[0] 1561, RACC[3]1562, RACC[0] 1563, RACC[1] 1564, RACC[0] 1565. In depicted portion1560, data held in RACC[0] 1565 may be transferred to adder 1567 viamultiplexer 1568 and connection 1569. Also, data held in RACC[0] 1561(e.g., data previously stored in RACC[0] 1561, for example, by adder1567) may be supplied to adder 1567 via connection 1570. Note that indepicted embodiment 1560, RACC[0] 1565 may provide data to adder 1567via connection 1569 whereas in depicted portion 1500 (in FIG. 15A)RACC[3] 1501 may provide data to adder 1505 via connection 1508.

It should be noted with respect to the operation of embodiment 1560,that when the value read from ADC(s) 114 is zero (i.e. all bits are‘0’), the result of the MAC operation may store the same previous valuefor that channel, stored in RACC[0] 1565, into accumulator registerRACC[4] 1561 before the new MAC operation begins. This may beaccomplished through multiplexer 1568 and adder 1567, which may,however, result in also adding whatever value is present in shifter 1566(the current filter coefficient). Thus, in some embodiments, additionalcontrol logic may be added to gate off the value of the shifter or tobypass the adder in such cases. It should also be noted that for thesake of clarity and simplicity, specific control signals that may beused in processing samples and rotating results, and specific controlsignals that may be used in implementing the MAC operation on theaccumulator registers—which may be a part of the rotating registersthemselves—have been omitted from FIGS. 15A and 15D.

More specific to embodiment 1560, a control signal may be provided tomultiplexer 1568 to select the data input coming to multiplexer 1568from RACC[0] 1565 on the first bit from the ADC that equals one. Thisfirst addition may recover the stored value for the channel from RACC[0]1565 and store the intermediate result in RACC[4] 1561. However,subsequent additions (one addition for each bit from the ADC that equalsone) may use the intermediate value from RACC[4] 1561 in order tocomplete the MAC operation. In other words, the control signal mayselect the data input coming to multiplexer 1568 from RACC[4] 1561 inthese cases. This sequence of additions (as many as there are ones onthe ADC value) may be considered a Store operation, which may bealternated with a shift operation. It should also be noted that thiscontrol signal may not cover the case when the ADC value has no ones(the case referenced above), in which case the Store operation may beperformed without affecting the value of RACC[0] 1565, which is to betransferred to RACC[4] 1561.

FIG. 15E depicts a table 1580 that illustrates the changing contents ofaccumulator registers (e.g., RACC[4:0] of FIG. 15D) and the movement ofdata between accumulator registers (e.g., between registers RACC[4]1561, RACC[3] 1562, RACC[2] 1563, RACC[1] 1564 and RACC[0] 1565) duringthe processing of the plurality of data samples 1512 according tovarious embodiments (e.g., embodiments that may correspond to depictedembodiment 1560).

Cells in table 1580 are shaded according to the contents of theindividual cell. Cells are shaded in a similar fashion to the pluralityof samples 1512. For example, cells that may be associated with channel“A” or that may be associated with a sample corresponding to channel “A”(e.g., sample “A0” 1520 or sample “A1” 1524) are cross-hatch shaded.Also, cells that may be associated with channel “C” or that may beassociated with a sample corresponding to channel “C” (e.g., sample “C0”1522 or sample “C1” 1526) are diagonally shaded.

Table 1580 has five columns, where each column may display the contentsof a respective accumulator register. In table 1580, column 1575 maydisplay the contents of the RACC[4] register 1561, column 1574 maydisplay the contents of the RACC[3] register 1562, column 1573 maydisplay the contents of the RACC[2] register 1563, column 1572 maydisplay the contents of the RACC[1] register 1564 and column 1571 maydisplay the contents of the contents of the RACC[0] register 1565. Table1580 is also organized by rows and each row may display the contents ofthe five RACC registers at successive points during the processing ofsamples 1512. The top row 1581 of table 1580 may, for example, depictRACC[4:0] register contents prior to processing sample sequence 1514 andthe bottom row 1597 may depict RACC[4:0] register contents subsequent toprocessing sample sequence 1516.

In table 1580, top row 1581 may depict RACC[4:0] contents afterinitialization values have been stored in registers, initializationvalues may be stored in each register to correspond to a channel. Forexample, an initialization value “INA” corresponding to channel “A” maybe stored in RACC[0] register 1565 (and also in RACC[4] register 1561)and an initialization value “IND” corresponding to channel “D” may bestored in RACC[3] register 1562 and similarly for initialization values“INC” and “INB”. The initialization values “INA”, “INB”, “INC” and “IND”may be various values (e.g., they may be the same value, they may bezero, they may correspond to previous samples etc.) The remaining rowsin table 1580 may be partitioned into groups of two rows (e.g., rows1586 and 1587, rows 1594 and 1595), and each group of two rows maycorrespond to a sample of the plurality of samples 1512.

The top row of each group of two rows may depict accumulator registercontents after a sample has been processed and a corresponding resulthas been stored. For example, row 1582 “A0 store” may depict thecontents of accumulator registers RACC[4:0] after sample “A0” 1520 hasbeen processed and result “A0R” has been stored. Similarly, row 1594 “C1store” may depict the contents of accumulator registers RACC[4:0] aftersample “C1” has been processed and a result “C1R” has been stored. Intable 1580, the result of processing a sample “X#” (where X may be “A”,“B”, “C” or “D” and “#” may be “0”, “1”) of the plurality of samples1512, may be designated “X#R”.

The bottom row of each group of two rows may depict accumulator registercontents after the contents of accumulator registers RACC[4:0] have beenshifted. For example, row 1583 “A0 shift” may depict the contents ofaccumulator registers RACC[4:0] after the register contents shown in row1582 “A0 store” have been shifted. Similarly, row 1595 “C1 shift” maydepict the contents of accumulator registers RACC[4:0] after theregister contents shown in row 1594 “C1 store” have been shifted. Asdepicted in FIG. 15E, in some embodiments, after each successive samplein each sample sequence is processed (e.g., stored), the contents of theresult accumulator registers may be shifted.

In some embodiments, (e.g., as depicted in FIGS. 15B, 15D and 15E), thenumber of accumulator registers (e.g., RACC[4:0], 5 registers) mayexceed (e.g., by one) the number of samples in a sample sequence (e.g.,4), the contents of the accumulator registers (e.g., RACC[4:0]) may beshifted once per result store operation (e.g., after each result storeoperation, before each store operation), the result accumulators may becoupled in series (e.g., in sequence) and an output of the trailing(e.g., last in series) accumulator register (e.g., RACC[0]] may becoupled to an input of the adder 1567 so that shifted result data may beaccumulated, e.g., with new result data, with new result datacorresponding to the same channel). In some embodiments, the contents ofthe result accumulator registers may be shifted in sequence with theorder of samples in sample sequences being processed (e.g., samplesequence 1514, 1516) in such a way that, for each sample beingprocessed, result data corresponding to one or more preceding samplesfrom the same channel is output from the last accumulator register,e.g., RACC[0] 1565 to adder 1567 via connection 1569 and multiplexer1568. This may allow, for example, results for the current sample to beaccumulated with one or more previous results (e.g., previous resultsfrom the same channel).

Shifting the contents of accumulator registers RACC[4:0] in sequencewith the successive processing of samples from the plurality of samples1512 may be observed in FIG. 15E. As shown in the row 1581, RACC[0] 1565may hold “INA” (e.g., an initialization value for channel “A”). Thevalue “INA” may be added (e.g., in adder 1567) to another value (e.g., avalue calculated for sample “A0” 1520) to produce a resultingaccumulated value (e.g., “A0R”) that may be stored in RACC[4] 1561 (asdepicted in row 1582), overwriting previous value “INA”. After the storeoperation of row 1582, result data may be shifted through RACC[4:0] sothat, for example, RACC[0] 1565 may now hold the value “INB” as depictedin row 1583. The value “INB” (e.g. an initialization value for channelB) held in RACC[0] 1565 may be supplied (e.g., to adder 1567 viaconnection 1569) to produce, for example, an accumulated value “B0R” forsample “B0” 1521, and accumulated value “B0R” may be stored into RACC[4]1561 overwriting “A0R”, as depicted in row 1584. Then the contents ofthe sequence of result accumulator registers may be shifted, and afterthe shifting the contents of RACC[4:0] may resemble row 1585. Aresulting value “C0R” corresponding to sample “C0” 1522 may be similarlygenerated and stored (e.g., as illustrated in row 1586), followed by ashift of accumulated data (e.g., as illustrated in row 1587). Similarly,for sample “D0” 1523, a resulting value “D0R” may be generated andstored (e.g., as illustrated in row 1588), followed by a shifting ofstored data (e.g., as illustrated in row 1589). By row 1589, all theinitialization data (e.g., channel initialization data “IND, INC, INB,INA”) held in the accumulator registers RACC[3:0] may be overwrittenwith resulting data (e.g., “D0R, C0R, B0R, A0R”) corresponding tosamples from sample sequence 1514.

After sample D0 has been processed, and resulting data shifted (e.g. row1589) the first sample of next sample sequence (e.g., sample “A1” 1524)may be processed. As shown in row 1589, RACC[0] 1565 may hold the value“A0R” the value resulting from processing sample A0 1520. The value“A0R” may be added (e.g., in adder 1567) to a value calculated forsample “A1” 1524 to produce a resulting accumulated value (e.g., “A1R”)that may be stored in RACC[4] 1561 (as depicted in row 1590),overwriting value “D0R”. After the store operation of row 1590, resultdata may be shifted through RACC[4:0] so that, for example, RACC[0] 1565may now hold the value “B0R” as depicted in row 1591. The value “B0R”(e.g., the value resulting from the processing of sample “B0”) held inRACC[0] 1565 may be supplied (e.g., to adder 1567 via connection 1569)to produce, for example, an accumulated value “B1R” for sample “B1”1525, and accumulated value “B1R” may be stored (e.g., as depicted inrow 1592) into RACC[4] 1561 overwriting “B0R”. After the store operationof row 1592, result data may be shifted through RACC[4:0] so that, forexample, RACC[0] 1565 may now hold the value “C0R” as depicted in row1593. A resulting value “C1R” corresponding to sample “C1” 1526 may besimilarly generated and stored (e.g., as illustrated in row 1594),followed by a rotation of stored data (e.g., as illustrated in row1595). Similarly, for sample “D1” 1527, a resulting value “D1R” may begenerated and stored (e.g., as illustrated in row 1596), followed by ashifting of stored data (e.g., as illustrated in row 1597). By row 1597,all the resulting data corresponding to sample sequence 1514 (e.g.,resulting data “D0R, C0R, B0R, A0R”) held in the accumulator registersRACC[3:0] may be overwritten with resulting data (e.g., “D1R, C1R, B1R,A1R”) corresponding to samples from sample sequence 1516. In thismanner, for each channel of a plurality of channels, resultscorresponding to successive samples from the channel may be accumulatedtogether.

In some embodiments, the leading register of the result accumulatorregisters (e.g., RACC[3] 1501, RACC[4] 1561) may be used to accumulatethe results of processing each sample. The results of processing eachsample may be considered to be a current effective sample, where aneffective sample may be, for example, an oversampling result and where acurrent effective sample may be, for example, an intermediate result inthe calculation (e.g., generation, production) of an oversampling value.

For example, in a system with sixteen times oversampling, sixteensamples may be successively weighted and the results accumulated toproduce one sample (e.g., a final effective sample). And, for eachsample position in a non-final sample sequence (e.g., sample sequencesone to fifteen), the results produced (e.g., intermediate results) maybe considered a current effective sample for that sample position. Forexample, during the processing of sequence 1514 in FIG. 15B, sample D01523 may be processed and corresponding result D0R (which may beconsidered to be the current effective sample for channel “D”) may bestored in RACC[4] (e.g., as depicted in line 1588 of FIG. 15E). And,during the processing of next successive sequence 1516 in FIG. 15B,sample D1 1527 (may be considered to be the current effective sample forchannel “D”) may be processed and corresponding result D1R may be storedin RACC[4] (e.g., as depicted in line 1596).

In some conditions, the results produced from processing a sample may beconsidered to be final results (e.g., may be considered final effectivesamples, may be considered oversampling results). For example, ifsequence 1516 is a final sequence of a specified number of samplesequences (e.g., sequence 1516 is the second sequence of a group of twosequences, sequence 1516 is the sixteenth sequence of a group of sixteensequences) then the results from processing each respective sample ofthe final sample sequence may be considered final results. And, afterthe final sample sequence has been processed, at least a portion of theaccumulator registers (e.g., a portion of RACC[3:0] in FIG. 15A, aportion of RACC[4:0] in FIG. 15D) may hold results corresponding torespective sample positions in the sample sequences. For example, ifsample sequence 1516 is a final sample sequence, then (as depicted inFIG. 15C) after sample D1 1527 has been processed and the resultsshifted, register RACC[3] 1501 may hold A1R which may be a finaleffective sample for channel “A”, register RACC[2] 1502 may hold D1Rwhich may be a final effective sample for channel “D”, register RACC[1]1503 may hold C1R which may be a final effective sample for channel “C”and register RACC[0] 1504 may hold B1R which may be a final effectivesample for channel “B”.

Similarly, as depicted in FIG. 15E for example, after sample D1 1527(e.g., from sample sequence 1516) has been processed and the resultsshifted, register RACC[3] 1562 may hold D1R which may be a finaleffective sample for channel “D”, register RACC[2] 1563 may hold C1Rwhich may be a final effective sample for channel “C”, register RACC[1]1564 may hold B1R which may be a final effective sample for channel “B”and register RACC[0] 1565 may hold A1R which may be a final effectivesample for channel “A”.

Furthermore, processing a sample may involve multiplying the sample by aweighting factor (e.g., a filter coefficient, a coefficient value). Insome embodiments (e.g., oversampling embodiments) multiple samples maybe multiplied by respective coefficient values and the resultsaccumulated. For example, in a system supporting sixteen timesoversampling, each of the sixteen samples may be successively weighted(e.g., multiplied by respective weighting coefficient) and the resultsaccumulated to produce a final effective sample. Accordingly, thesixteen coefficient values may be chosen (e.g., selected, predetermined,generated, used etc.) so that the sum of the sixteen coefficient valuesis equal to a specified value (e.g., one, a normalizing value, a scalingvalue). For example, in one embodiment, the following set of fourcoefficient values, totaling a value of one, (0.1, 0.4, 0.4, 0.1) may beused to weight four samples (e.g., to produce a final effective sample).

FIGS. 16A-16H and FIGS. 17A-17E

FIGS. 16A-16H and 17A-17E illustrate the generation of coefficientsaccording to various embodiments. FIGS. 16A-16H are a collection ofcharts related to a simple exemplary weighting function. The charts ofFIGS. 16A-16H illustrate that a weighting function may be constructed byconvolving rectangle functions. In addition, the charts of FIGS. 16A-16Hillustrate that a sufficiently differentiated weighting function may bea function consisting of a number of delta functions. In the charts ofFIGS. 16 and 17, function amplitude (e.g., function value) is shown onthe vertical axis and independent variable “t” shown on the horizontalaxis, where “t” may refer to time (e.g., time in milliseconds).

FIG. 16A depicts an exemplary weighting function (e.g., coefficientfunction) c(t) which may provide a coefficient value (e.g., sampleweighting value) during a specified time period (e.g., a time window, asampling window, an over-sampling window), that may be, for example, 8mS in duration. Since the weighting function c(t) may be the result ofconvolving a 2 ms rectangle with a 6 ms rectangle, it may be suitablefor generating a notch filter with a notch at 166.66 Hz (and itsharmonics) and another notch at frequency 500 Hz (and its harmonics).

FIG. 16B may depict a first order derivative function c′(t) of theweighting function c(t) depicted in FIG. 16A, where c′(t) may be a timederivative of c(t). The function c′(t) may provide the slope of functionc(t), which may be +1 when t falls between 1 mS and 3 mS and may be −1when t falls between 7 mS and 9 mS.

FIG. 16C may depict rectangle function f(t) that may, throughconvolution with a second function, create weighting function c(t).Function f(t), as depicted in chart 1620, may have a value of 1 when tfalls between 0 mS and 6 mS.

FIG. 16D may depict first order derivative function f′(t) of rectanglefunction f(t) as depicted in chart 1620. Since the slope of rectanglefunction f(t) may be considered infinite at time 0 mS and time 6 mS,derivative function f′(t), as depicted in chart 1630, may comprise deltafunctions at time 0 mS and time 6 mS.

FIG. 16E may depict rectangle function g(t) that may, throughconvolution with function f(t), create weighting function c(t). Functiong(t), as depicted in FIG. 16E, may have a value of 1 when t fallsbetween 1 mS and 3 mS.

FIG. 16F may depict a first order derivative function g′(t) of rectanglefunction g(t) depicted in FIG. 16E. Since the slope of rectanglefunction g(t) may be considered infinite at time 1 mS and time 3 mS,derivative function g′(t), as depicted in FIG. 16F, may comprise a deltafunction at time 1 mS and a delta function at time 3 mS.

FIG. 16G may depict the function f′(t)*g′(t) (where “*” denotes theconvolution operator) which may be produced, for example, by theconvolution of derivative functions f′(t) and g′(t). The functionf′(t)*g′(t), as depicted in FIG. 16G for example, may comprise twopositive delta functions (e.g., one at time 1 ms, one at time 9 mS) andtwo negative delta functions (e.g., one at time 3 mS, one at time 7 mS).

FIG. 16H may depict the function c″(t) which may be considered a firstorder derivative function of derivative function c′ (t) (as depicted inFIG. 16B for example) and which may also be considered a second orderderivative of function c(t) (as depicted FIG. 16A for example). Thefunction c″(t), as depicted in FIG. 16H may be similar (e.g. identical)to the function g′(t)*f′(t) as depicted FIG. 16G, as it may similarlycomprise two positive delta functions (e.g., one at time 1 ms, one attime 9 mS) and two negative delta functions (e.g., one at time 3 mS, oneat time 7 mS).

The charts in FIGS. 16A-16H may illustrate that a weighting function,e.g., weighting function c(t), that may correspond to a convolution ofrectangle functions, e.g., f(t)*g(t), may be successively differentiatedto produce a derivative function, e.g., c″(t), that may be comprised anumber of delta functions.

While exemplary function c(t), as depicted in FIG. 16A for example, maybe a simple weighting function corresponding to a convolution of tworectangle functions, more complicated weighting functions may besimilarly produced by convolving a larger number (e.g., 3, 6, etc.) ofrectangle functions. Furthermore, a weighting function corresponding tospecific number of convoluted rectangle functions (e.g., 3 rectanglefunctions, 6 rectangle functions, etc.) may be converted, for example,through a respectively similar or respectively identical number ofdifferentiations (e.g., 3 differentiations, 6 differentiations, etc.) toa respectively similar order derivative function (e.g., a 3^(rd) orderderivative function, 6^(th) order derivative function, etc.) comprisingdelta functions (e.g., consisting only of delta functions).

FIGS. 17A-17E may illustrate that a sequence of coefficient valuescorresponding to a weighting function may be produced from a basefunction that may correspond to a derivative of the weighting function.FIG. 17A may depict coefficient function c(t), as in FIG. 16A forexample. FIG. 17B may depict a 2^(nd) order derivative function c″(t) aspreviously depicted in FIG. 16H, for example; and c″(t) may represent abase function.

A number sequence 1702 corresponding to base function c″(t) may beproduced, for example as shown FIG. 17C. Each successive number innumber sequence 1702 may correspond to a value of base function c″(t) ata successively later time. For example, the first four numbers insequence 1702 (e.g., 0,1,0,−1) may respectively represent the number ofsuperimposed delta functions in base function c″(t) at 0 mS, 1 mS, 2 mSand 3 mS. It should be noted that the respective values of base functionc″(t) at 1 mS and 3 mS, for example, may be plus or minus “infinite”,stemming from representing continuous functions in the discrete domain.In other words, while the derivative of the edge of a rectangle would berepresented by infinity (for an infinitesimal time) in the continuousdomain, it would be represented by “1” in the discrete domain.

FIG. 17D depicts another number sequence 1704 that may correspond to anintegral (e.g., accumulation) of base function c″(t). In someembodiments, number sequence 1704 may be generated (e.g., generatedsequentially, calculated, generated coincidentally with number sequence1702 being generated) from the number sequence 1702. In someembodiments, each number in number sequence 1704 may correspond to arespective, similarly positioned number in number sequence 1702. Forexample, the first, second and third numbers in number sequence 1704 mayrespectively correspond to the first, second and third numbers in numbersequence 1702.

Each number in number sequence 1704 may be generated, according tocertain embodiments, by accumulating (e.g., integrating) numbers innumber sequence 1702 that precede (and include) a correspondingrespective number (e.g., similarly positioned number) in number sequence1702. For example, the fourth number in number sequence 1704 (e.g.,zero) may be generated by accumulating the first four numbers in numbersequence 1702 (e.g., zero, plus one, zero, minus one). Comparingsuccessive numbers in number sequence 1704 to successive values offunction c′(t) (e.g., as depicted in FIG. 16B) the number sequence 1704,as generated, for example, by the accumulation of a sequence of numberscorresponding to base function c″(t), may be found to correspond tofunction c′(t), a first integral function of base function c″(t).

In a similar fashion, each number in number sequence 1706 shown in FIG.17E may be generated, according to certain embodiments, by accumulating(e.g., integrating) numbers in number sequence 1704 that precede (andinclude) a corresponding respective number (e.g., similarly positionednumber) in number sequence 1704. For example, the fourth number innumber sequence 1706 (e.g., two) may be generated by accumulating thefirst four numbers in number sequence 1704 (e.g., zero, plus one, plusone, zero). Comparing successive numbers in number sequence 1706 tosuccessive values of function c(t) (e.g., as depicted in FIG. 17A) thenumber sequence 1706, as generated, for example, by the accumulation ofa sequence of numbers corresponding to function c′(t), may be found tocorrespond to weighting function c(t), e.g., a first integral functionof function c′(t). Thus, by a process of two successive accumulations, asequence of numbers corresponding to weighting function c(t) may beproduced (e.g., sequentially, one at a time, in real time) from a basefunction corresponding to a 2^(nd) order derivative of the weightingfunction c(t).

FIG. 18

FIG. 18 depicts a flow chart 1800 that illustrates a method that may beused for processing data samples from multiple channels according tovarious embodiments. The method shown in FIG. 18 may be used inconjunction with any of the systems or devices shown in the aboveFigures, among other devices. In various embodiments, some of the methodelements shown may be performed concurrently, performed in a differentorder than shown, or omitted.

As depicted in FIG. 18, the method may include block 1802 in which aplurality of data samples may be obtained (e.g., received, read fromstorage, read from a buffer, received in a sequence) from a plurality ofchannels. In some embodiments, the plurality of channels may be anordered set of channels (e.g., each channel in the set different fromother channels in the set and the channels arranged in a specifiedorder).

The plurality of data samples may correspond to a plurality of datasets, where each data set may include a plurality of data samples andwhere each data set may correspond to data samples from a specifiedchannel. Obtaining the plurality of data samples may involve receiving,in a sequence, each data sample of the plurality of data sets. Theplurality of data samples may be a sequence of data samples (e.g., theplurality of data samples may be received as a sequence of datasamples), and data samples may be arranged (e.g., ordered, received)within the sequence of data samples according to the time acorresponding signal was sampled to create the respective data sample.

Associated with each sample may be a respective sample time, and eachsample time may be measured relative a specified reference point (e.g.,relative the start of a corresponding integration period, relative tothe sample time of a leading sample in an integration period). Thespecified reference point may be common to (e.g., the same for) samplesfrom different channels. The specified reference point may be shared bysamples corresponding to the same integration period. Further, eachsuccessive data sample in the sequence of data samples may correspond toa successively later sampling time (e.g., a sampling time greater by anamount corresponding to a sampling period). And data samples may bearranged within the sequence of data samples to correspond to the orderof channels within the ordered set of channels so that, for example,adjacent data samples in the sequence of data samples correspond todifferent channels within the ordered set of channels.

The method may also, in some embodiments, include block 1804 in which atime-dependent coefficient value may be determined (e.g., generated,produced, calculated) for each data sample in the plurality of obtaineddata samples. The time dependent coefficient may be determined by firstdetermining (e.g., identifying) a time associated with the data sample.In some embodiments, the time associated with a data sample (e.g., arelative sample time) may be indicated (e.g., identified) by theposition of the data sample within a sequence of data samples. And, incertain embodiments, the position of a current data sample within asequence of data samples may be identified by the current value of anindex register that may be configured to count the number of datasamples obtained (e.g., received) since the index register was last setto a specified value indicative of a leading data sample position withina sequence of data samples. In one or more embodiments, a coefficientvalue for a data sample (e.g., a current data sample) may be determined(e.g., produced, generated) using the current value of the indexregister.

In certain embodiments, a group of two or more consecutive samples inthe sequence of data samples may correspond to different channels.Coefficients for each respective data sample of the group of two or moredata samples (e.g., coefficients as determined by the sample time ofeach data sample and/or position of the data sample within the sequenceof data samples) may be different so that, for example, neighboring(e.g., adjacent) data samples from different channels may be weighteddifferently. In some embodiments, coefficient values corresponding to aplurality of adjacent data samples (e.g., two adjacent samples, fiveadjacent data samples, two or more adjacent data samples correspondingto different channels) may each have different values. Also, for atleast a portion of the determined coefficient values, each obtainedcoefficient value may be different from a most recent previouslydetermined coefficient value. In some embodiments, the value of atime-dependent coefficient corresponding to a data sample may alsodepend on the channel corresponding to the data sample (e.g., tocustomize filtering according to a channel) and determining atime-dependent coefficient value may include identifying a correspondingchannel for each obtained data sample.

In certain embodiments, the method may also include block 1806, whichmay follow block 1804 as depicted in FIG. 18. In block 1806, a timedependent coefficient may be applied to each data sample (e.g., eachrespective data sample corresponding to the time dependent coefficient)of the plurality of obtained data samples to produce a plurality (e.g.,a plurality equal in number to the plurality of obtained data samples)of weighted data samples. A time dependent coefficient may be applied toa data sample in various ways and according to various embodiments. Forexample, a data sample may be multiplied by a corresponding coefficientvalue and/or a data sample may be arithmetically combined with acorresponding coefficient value and/or a data sample may be logicallycombined with the corresponding coefficient value and/or a data samplemay be value limited according to the corresponding coefficient value.

According to one of more embodiments, the method may also include block1808 which may (e.g., as depicted in FIG. 18) follow block 1806. Incertain embodiments, block 1808 may involve generating, for each of twoor more data channels in the plurality of data channels, an effectivedata sample from two or more weighted data samples corresponding to therespective data channel. An effective data sample may be generated for aplurality of data samples falling within a sampling window (e.g., aperiod used to repetitively sample signals corresponding to a pluralityof channels). An effective data sample may be generated for each channelof the two or more channels and each effective data sample may have acorresponding effective sample time. A plurality of effective datasamples (e.g., a plurality of effective data samples where eacheffective data sample corresponds to a different channel) thatcorrespond to the same sampling window (e.g., period for repetitivelysampling signals corresponding to a plurality of channels) may havesimilar effective sampling times. By applying a weighting coefficientthat corresponds to the sample time (e.g., the sample time measuredrelative to a common reference for all channels) of each data sample,the effective sample times of a plurality of effective data samples(e.g., where each different effective data sample in the plurality ofeffective data samples corresponds to a different channel) may be moreclosely aligned.

Further modifications and alternative embodiments of various aspects ofthe invention may be apparent to those skilled in the art in view ofthis description. Accordingly, this description is to be construed asillustrative only and is for the purpose of teaching those skilled inthe art the general manner of carrying out the invention. It is to beunderstood that the forms of the invention shown and described hereinare to be taken as embodiments. Elements and materials may besubstituted for those illustrated and described herein, parts andprocesses may be reversed, and certain features of the invention may beutilized independently, all as would be apparent to one skilled in theart after having the benefit of this description of the invention.Changes may be made in the elements described herein without departingfrom the spirit and scope of the invention as described in the followingclaims.

Moreover, regarding the signals described herein, those skilled in theart will recognize that a signal can be directly transmitted from afirst block to a second block, or a signal can be modified (e.g.,amplified, attenuated, delayed, latched, buffered, inverted, filtered,or otherwise modified) between the blocks. Although the signals of theabove described embodiment are characterized as transmitted from oneblock to the next, other embodiments of the present disclosure mayinclude modified signals in place of such directly transmitted signalsas long as the informational and/or functional aspect of the signal istransmitted between blocks. To some extent, a signal input at a secondblock can be conceptualized as a second signal derived from a firstsignal output from a first block due to physical limitations of thecircuitry involved (e.g., there will inevitably be some attenuation anddelay). Therefore, as used herein, a second signal derived from a firstsignal includes the first signal or any modifications to the firstsignal, whether due to circuit limitations or due to passage throughother circuit elements which do not change the informational and/orfinal functional aspect of the first signal.

The foregoing description, for purposes of explanation, has beendescribed with reference to specific embodiments. However, theillustrative discussions above are not intended to be exhaustive or tolimit the invention to the precise forms disclosed. Many modificationsand variations are possible in view of the above teachings. Theembodiments were chosen and described in order to best explain theprinciples of the invention and its practical applications, to therebyenable other skilled in the art to best utilize the invention andvarious embodiments with various modifications as may be suited to theparticular use contemplated.

Although the embodiments above have been described in considerabledetail, numerous variations and modifications will become apparent tothose skilled in the art once the above disclosure is fully appreciated.It is intended that the following claims be interpreted to embrace allsuch variations and modifications.

The invention claimed is:
 1. A method for processing data samplescorresponding to a plurality of data channels, the method comprising:obtaining, by data acquisition circuitry, a plurality of data samplesderived from corresponding electrical signals received by the pluralityof data channels, said obtaining comprising successively receiving arespective data sample corresponding to each data channel serially at aserial input port, said obtaining further comprising performing saidsuccessively receiving a plurality of times during a specified timeperiod, wherein each respective data sample is obtained at a respectivesample time, and wherein each respective sample time is relative to asingle specified reference point in time; and for each respective datasample: determining, by a data processing circuit, a respectivechannel-dependent coefficient value corresponding to the respectivesample time at which the respective data sample is obtained; andapplying by the data processing circuit, the respectivechannel-dependent coefficient value to the respective data sample tophase align the plurality of data channels.
 2. The method of claim 1,wherein the single specified reference point in time is located withinthe specified time period.
 3. The method of claim 1, wherein the singlespecified reference point in time corresponds to a start of thespecified time period.
 4. The method of claim 1, wherein said obtainingthe plurality of data samples comprises receiving the plurality of datasamples at a specified rate.
 5. The method of claim 1, wherein saidsuccessively receiving is according to a specified order correspondingto a specified ordering of the plurality of data channels.
 6. The methodof claim 1, wherein said applying comprises multiplying the respectivedata sample by the respective channel-dependent coefficient value toproduce a respective weighted data sample.
 7. The method of claim 6,further comprising: for each data channel of one or more data channelsof the plurality of data channels: generating a respective effectivedata sample from two or more respective weighted data samplescorresponding to the data channel.
 8. The method of claim 7, whereinsaid generating comprises arithmetically combining the two or morerespective weighted data samples.
 9. An apparatus for processing asequence of data samples, the apparatus comprising: a serial input portconfigured to serially receive a plurality of data samples derived fromcorresponding electrical signals that are received by a plurality ofdata channels, wherein to serially receive the plurality of datasamples, the serial input port is configured to: successively receive arespective data sample corresponding to each data channel a plurality oftimes during a specified time period, wherein each respective datasample is obtained at a respective sample time, and wherein eachrespective sample time is relative to a single specified reference pointin time; and first circuitry configured to: for each respective datasample, determine a respective channel-dependent coefficient valuecorresponding to the respective sample time at which the respective datasample is obtained; and for each respective data sample, apply therespective channel-dependent coefficient value to the respective datasample to phase align the plurality of data channels.
 10. The apparatusof claim 9, wherein the single specified reference point in time islocated within the specified time period.
 11. The apparatus of claim 9,wherein the single specified reference point in time corresponds to astart of the specified time period.
 12. The apparatus of claim 9,wherein the serial input port is configured to receive the plurality ofdata samples at a specified rate.
 13. The apparatus of claim 9, whereinthe serial input port is configured to successively receive a respectivedata sample corresponding to each data channel in a specified ordercorresponding to a specified ordering of the plurality of data channels.14. The apparatus of claim 9, wherein to apply the respectivechannel-dependent coefficient value to the respective data sample, thefirst circuitry is configured to multiply the respective data sample bythe respective channel-dependent coefficient value to produce arespective weighted data sample.
 15. The apparatus of claim 14, whereinthe first circuitry is further configured to: for each data channel ofone or more data channels of the plurality of data channels, generate arespective effective data sample from two or more respective weighteddata samples corresponding to the data channel.
 16. The apparatus ofclaim 15, wherein to generate a respective effective data sample fromtwo or more respective weighted data samples corresponding to the datachannel, the first circuitry is configured to arithmetically combine thetwo or more respective weighted data samples.
 17. A data acquisition andprocessing system, the system comprising: a front-end circuit configuredto provide a serial data stream comprising a plurality of data samplesderived from corresponding electrical signals received by a plurality ofdata channels; and a data processing circuit having a serial input portand configured to: serially receive the serial data stream at the serialinput port, wherein to serially receive the serial data stream, the dataprocessing circuit is configured to successively receive a respectivedata sample corresponding to each data channel a plurality of timesduring a specified time period, wherein each data sample of theplurality of data samples is obtained at a respective sample time, andwherein each respective sample time is relative to a single specifiedreference point in time; and for each respective data sample, determinea respective channel-dependent coefficient value corresponding to therespective sample time at which the respective data sample is obtained;and for each respective data sample, apply the respectivechannel-dependent coefficient value to the respective data sample tophase align the plurality of data channels.
 18. The system of claim 17,wherein the front-end circuit comprises: an analog front end modulecomprising the plurality of data channels, wherein each data channel ofthe plurality of data channels is configured to receive a correspondingrespective analog signal; wherein the data processing circuit comprisesan analog-to-digital converter (ADC) configured to generate theplurality of data samples based on each corresponding respective analogsignal.
 19. The system of claim 17, wherein the front-end circuit isconfigured to generate the plurality of data samples in a specifiedorder corresponding to a specified ordering of the plurality of datachannels.
 20. The system of claim 17, wherein the data processingcircuit is configured to: multiply the respective data sample by therespective channel-dependent coefficient value to produce a respectiveweighted data sample when applying the respective channel-dependentcoefficient value to the respective data sample; and for each datachannel of one or more data channels of the plurality of data channels,generate a respective effective data sample from two or more respectiveweighted data samples corresponding to the data channel.